Wireless devices and systems including examples of full duplex transmission using neural networks or recurrent neural networks

ABSTRACT

Examples described herein include systems and methods which include wireless devices and systems with examples of full duplex compensation with a self-interference noise calculator. The self-interference noise calculator may be coupled to antennas of a wireless device and configured to generate adjusted signals that compensate self-interference. The self-interference noise calculator may include a network of processing elements configured to combine transmission signals into intermediate results according to input data and delayed versions of the intermediate results. Each set of intermediate results may be combined in the self-interference noise calculator to generate a corresponding adjusted signal. The adjusted signal is received by a corresponding wireless receiver to compensate for the self-interference noise generated by a wireless transmitter transmitting on the same frequency band as the wireless receiver is receiving.

BACKGROUD

There is interest in moving wireless communications to “fifthgeneration” (5G) systems 5G promises increased speed and ubiquity, butmethodologies for processing 5G wireless communications have not yetfully been set. Example 5G systems may be implemented usingmultiple-input multiple-output (MIMO) techniques, including “massiveMIMO” techniques, in which multiple antennas (more than a certainnumber, such as 8 in the case of example MIMO systems) are utilized fortransmission and/or receipt of wireless communication signals.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a schematic illustration of a system arranged in accordancewith examples described herein.

FIG. 2 is a schematic illustration of an electronic device arranged inaccordance with examples described herein.

FIG. 3 is a schematic illustration of a wireless transmitter.

FIG. 4 is a schematic illustration of wireless receiver.

FIG. 5A is a schematic illustration of an example self-interferencenoise calculator arranged as a neural network in accordance withexamples described herein.

FIG. 5B is a schematic illustration of a recurrent neural networkarranged in accordance with examples described herein.

FIGS. 5C-5E are schematic illustrations of example self-interferencenoise calculators arranged as recurrent neural networks in accordancewith examples described herein.

FIG. 6 is a schematic illustration of an electronic device arranged inaccordance with examples described herein

FIG. 7 is a schematic illustration of a full duplex compensation methodarranged in accordance with examples described herein.

FIG. 8 is a flowchart of a method arranged in accordance with examplesdescribed herein.

FIG. 9 is a schematic illustration of a wireless communications systemarranged in accordance with aspects of the present disclosure.

FIG. 10 is a schematic illustration of another wireless communicationssystem arranged in accordance with aspects of the present disclosure.

DETAILED DESCRIPTION

Full duplex communication may be desirable for a variety of devices.Full duplex communication generally may refer to an ability to both sendand receive transmissions, in some cases simultaneously and/or partiallysimultaneously. In examples of systems employing full duplexcommunication, it may be desirable to cancel interference generated byother antennas in the system. Examples described herein may compensatefor interference generated by other antennas co-located on the samephysical device or system (e.g., interference created by an antenna on aMIMO device). In the example of frequency duplexing (FD), an antennatransmitting a transmission on a certain frequency band may createinterference for an antenna, co-located on the same device, receiving atransmission on the same frequency band. Such interference may bereferred to as self-interference. Self-interference may disrupt theaccuracy of signals transmitted or received by the MIMO device. Examplesdescribed herein may compensate for self-interference at an electronicdevice, which may aid in achieving full complex transmission. A networkof processing elements may be used to generate adjusted signals tocompensate for self-interference generated by the antennas of theelectronic device.

5G systems may advantageously make improved usage of full duplextransmission mode, for example, to improve spectrum efficiency.Frequency bands in some systems may be assigned by regulatoryauthorities such as the Federal Communication Commission (FCC).Assignments may be made, for example, according to differentapplications such as digital broadcasting and wireless communication.These licensed and assigned frequencies may be wasted if there is simplytime-division duplex (TDD), frequency-division duplex (FDD) orhalf-duplex FDD mode, which are duplexing modes often used in existingwireless applications. Such modes may not be acceptable when improvedefficiency is demanded from the wireless spectrum. Moreover, with thefast development of digital transmission and communications, there arefewer and fewer unlicensed frequency bands and it may be advantageous touse those licensed frequency bands in a full duplex transmission mode.For example, the FCC has officially proposed to open some UHF bands forunlicensed uses and is also considering how to use the frequency bandswhich are over 6 GHz (e.g. millimeter wave bands). Examples describedherein may be utilized to achieve full duplex transmission in someexamples on existing frequency bands including the aforementionedunlicensed frequency bands and 6 GHz bands. Full-duplex (FD)transmission may allow a wireless communication system to transmit andreceive the signals, simultaneously, in the same frequency band. Thismay allow FD-based 5G systems to the spectrum efficiency of anyfrequency band.

Examples described herein include systems and methods which includewireless devices and systems with a self-interference noise calculator.The self-interference noise calculator may utilize a network ofprocessing elements to generate a corresponding adjusted signal forself-interference that an antenna of the wireless device or system isexpected to experience due to signals to be transmitted by anotherantenna of the wireless device or system. Such a network of processingelements may combine transmission signals to provide intermediateprocessing results that are further combined, based on respectiveweights, to generate adjusted signals. The network of processingelements may be referred to as a neural network. In some implementationswith delayed versions of intermediate processing results being utilized,such a network of processing elements may be referred to as a recurrentneural network. A respective weight vector applied to the intermediateprocessing result may be based on an amount of interference expected forthe respective transmission signal from the corresponding intermediateprocessing result. In some examples, a self-interference noisecalculator may include bit manipulation units,multiplication/accumulation (MAC) processing units, and/or memorylook-up (MLU) units. For example, layers of MAC processing units mayweight the intermediate processing results using a plurality ofcoefficients (e.g., weights) based on a minimized error for the all orsome of the adjustment signals that may generated by a self-interferencenoise calculator. In minimizing the error for the adjustment signals, awireless device or system may achieve full duplex transmission utilizingthe self-interference noise calculator.

Examples described herein additionally include systems and methods whichinclude wireless devices and systems with examples of mixing input datawith such coefficient data in multiple layers ofmultiplication/accumulation units (MAC units) and corresponding memorylook-up units (MLUs). For example, a number of layers of MAC units maycorrespond to a number of wireless channels, such as a number ofchannels received at respective antennas of a plurality of antennas. Inaddition, a number of MAC units and MLUs utilized is associated with thenumber of channels. For example, a second layer of MAC units and MLUsmay include m-1 MAC units and MLUs, where m represents the number ofantennas, each antenna receiving a portion of input data,Advantageously, in utilizing such a hardware framework, the processingcapability of generated output data may be maintained while reducing anumber of MAC units and MLUs, which are utilized for such processing inan electronic device. In some examples, however, where board space maynot be limited, a hardware framework may be utilized that includes m MACunits and m MLUs in each layer, where m represents the number ofantennas.

Multi-layer neural networks (NNs) and/or multi-layer recurrent neuralnetworks (RNNs) may be used to transmit wireless input data (e.g., aswireless input data to be transmitted via an antenna). The NNs and/orRNNs may have nonlinear mapping and distributed processing capabilitieswhich may be advantageous in many wireless systems, such as thoseinvolved in processing wireless input data having time-varying wirelesschannels (e.g., autonomous vehicular networks, drone networks, orInternet-of-Things (IoT) networks), In this manner, neural networksand/or recurrent neural networks described herein may be used toimplement full duplex communication for various wireless protocols(e.g., 5G wireless protocols), thereby cancelling self-interferencegenerated by other antennas in the system.

In cancelling self-interference using RNNs, wireless systems and devicesdescribed herein may increase capacity of their respective wirelessnetworks, with such systems being more invariant noise to thantraditional wireless systems that do not use RNNs (e.g., utilizingtime-delayed versions of processing results). For example, the recurrentneural networks may be used to reduce self-interference noise that willbe present in transmitted signals (e.g., transmitter output data) basedpartly on the signals to be transmitted. Using time-delayed versions ofprocessing results in an RNN of transmitter output data, theself-interference noise introduced in the time and frequency domains maybe compensated, as the RNN utilizes respective time and frequencycorrelations with respect to the time-delayed versions of the input data(e.g., transmitter output data). In this manner, recurrent neuralnetworks may be used to reduce and/or improve errors which may beintroduced by self-interference noise. Advantageously, with such animplementation, wireless systems and devices implementing such RNNsincrease capacity of their respective wireless networks becauseadditional data may be transmitted in such networks, which would nototherwise be transmitted due to the effects of self-interference noise,e.g., which limits the amount of data to be transmitted due tocompensation schemes in traditional wireless systems,

FIG. 1 is a schematic illustration of a system arranged in accordancewith examples described herein. System 100 includes electronic device102, electronic device 110, antenna 101, antenna 103, antenna 105,antenna 107, antenna 121, antenna 123, antenna 125, antenna 127,wireless transmitter 131, wireless transmitter 133, wireless receiver135 and, wireless receiver 137. The electronic device 102 may includeantenna 121, antenna 123, antenna 125, antenna 127, wireless transmitter111, wireless transmitter 113, wireless receiver 115, and wirelessreceiver 117. The electronic device 110 may include antenna 101, antenna103, antenna 105, and antenna 107. In operation, electronic devices 102,110 can operate in a full duplex transmission mode between therespective antennas of each electronic device. In an example of a fullduplex transmission mode, wireless transmitter 131 coupled to antenna121 may transmit to antenna 105 coupled to wireless receiver 115, while,at the same time or during at least a portion of the same time, wirelesstransmitter 111 coupled to antenna 101 may transmit to antenna 127coupled to wireless receiver 137, in some examples at a same frequencyor in a same frequency band. Self-interference received by antenna 127or antenna 105 from the respective transmissions at antenna 121 andantenna 101 may be compensated by the systems and methods describedherein. Self-interference may generally refer to any wirelessinterference generated by transmissions from antennas of an electronicdevice to signals received by other antennas, or same antennas, on thatsame electronic device.

Electronic devices described herein, such as electronic device 102 andelectronic device 110 shown in FIG. 1 may be implemented using generallyany electronic device for which communication capability is desired. Forexample, electronic device 102 and/or electronic device 110 may beimplemented using a mobile phone, smartwatch, computer (e.g. server,laptop, tablet, desktop), or radio. In some examples, the electronicdevice 102. and/or electronic device 110 may be incorporated into and/orin communication with other apparatuses for which communicationcapability is desired, such as but not limited to, a wearable device, amedical device, an automobile, airplane, helicopter, appliance, tag,camera, or other device.

While not explicitly shown in FIG. 1, electronic device 102 and/orelectronic device 110 may include any of a variety of components in someexamples, including, but not limited to, memory, input/output devices,circuitry, processing units (e.g. processing elements and/orprocessors), or combinations thereof. For example, electronic device 102or electronic device 110 may each implement one or more processing unitsdescribed herein, such as a processing unit 512 with reference to FIGS.5C-5E, or any combinations thereof.

The electronic device 102 and the electronic device 110 may each includemultiple antennas. For example, the electronic device 102 and electronicdevice 110 may each have more than two antennas. Three antennas each areshown in FIG. 1, but generally any number of antennas may be usedincluding 2, 3, 4, 5, 6, 7, 8, 9, 10, 11, 12, 13, 14, 15, 16, 32, or 64antennas. Other numbers of antennas may be used in other examples. Insome examples, the electronic device 102 and electronic device 104 mayhave a same number of antennas, as shown in FIG. 1, In other examples,the electronic device 102 and electronic device 110 may have differentnumbers of antennas. Generally, systems described herein may includemultiple-input, multiple-output (“MIMO”) systems. MIMO systems generallyrefer to systems including one or more electronic devices which transmittransmissions using multiple antennas and one or more electronic deviceswhich receive transmissions using multiple antennas. In some examples,electronic devices may both transmit and receive transmissions usingmultiple antennas. Some example systems described herein may be “massiveMIMO” systems, Generally, massive MIMO systems refer to systemsemploying greater than a certain number (e.g. 8) antennas to transmitand/or receive transmissions. As the number of antennas increase, so togenerally does the complexity involved in accurately transmitting and/orreceiving transmissions.

Although two electronic devices (e.g. electronic device 102 andelectronic device 110) are shown in FIG. 1, generally the system 100 mayinclude any number of electronic devices.

Electronic devices described herein may include receivers, transmitters,and/or transceivers. For example, the electronic device 102 of FIG. 1includes wireless transmitter 131 and wireless receiver 135, and theelectronic device 110 includes wireless transmitter 111 and wirelessreceiver 115. Generally, receivers may be provided for receivingtransmissions from one or more connected antennas, transmitters may beprovided for transmitting transmissions from one or more connectedantennas, and transceivers may be provided for receiving andtransmitting transmissions from one or more connected antennas. Whileboth electronic devices 102, 110 are depicted in FIG. 1 with individualwireless transmitter and individual wireless receivers, it can beappreciated that a wireless transceiver may be coupled to antennas ofthe electronic device and operate as either a wireless transmitter orwireless receiver, to receive and transmit transmissions. For example, atransceiver of electronic device 102 may be used to providetransmissions to and/or receive transmissions from antenna 121, whileother transceivers of electronic device 110 may be provided to providetransmissions to and/or receive transmissions from antenna 101 andantenna 103. Generally, multiple receivers, transmitters, and/ortransceivers may be provided in an electronic device—one incommunication with each of the antennas of the electronic device. Thetransmissions may be in accordance with any of a variety of protocols,including, but not limited to 5G signals, and/or a variety ofmodulation/demodulation schemes may be used , including, but not limitedto: orthogonal frequency division multiplexing (OFDM), filter bankmulti-carrier (FBMC), the generalized frequency division multiplexing(GFDM), universal filtered multi-carrier (UFMC) transmission, hiorthogonal frequency division multiplexing (BFDM), sparse code multipleaccess (SCMA), non-orthogonal multiple access (NOMA), multi-user sharedaccess (MUSA) and faster-than-Nyquist (FTN) signaling withtime-frequency packing. In some examples, the transmissions may be sent,received, or both, in accordance with 5G protocols and/or standards.

Examples of transmitters, receivers, and/or transceivers describedherein, such as the wireless transmitter 131 and the wirelesstransmitter 111 may be implemented using a variety of components,including, hardware, software, firmware, or combinations thereof. Forexample, transceivers, transmitters, or receivers may include circuitryand/or one or more processing units (e.g. processors) and memory encodedwith executable instructions for causing the transceiver to perform oneor more functions described herein (e.g. software)

FIG. 2 is a schematic illustration 200 of an electronic device 110arranged in accordance with examples described herein. The electronicdevice 110 may also include self-interference noise calculator 240,compensation component 245, and compensation component 247.Self-interference noise calculator 240 and wireless transmitter 111, 113may be in communication with one another. Each wireless transmitter 111,113 may be in communication with a respective antenna, such as antenna101, antenna 103. Each wireless transmitter 111, 113 receives arespective signal to be transmitted, such as signals to be transmitted211, 213. The wireless receivers 115, 117 may process the signals to hetransmitted 211, 213 with the operations of a radio-frequency (RF)front-end to generate transmitter output data x₁(n), x₂(n) 221, 223. Thewireless transmitter 111, 113 may process the signals to be transmitted211, 213 as a wireless transmitter 300, for example.

Self-interference noise calculator 240 and compensation components 245,247 may be in communication with one another. Each wireless receiver maybe in communication with a respective antenna, such as antenna 105, 107and a respective compensation component, such as compensation component245, 247. In some examples, a wireless transmission received at antennas105, 107 may be communicated to wireless receiver 115, 117 aftercompensation of self-interference by the respective compensationcomponent 245, 247. Each wireless receiver 115, 117 processes thereceived and compensated wireless transmission to produce a respectiveprocessed received signal, such as processed received signals 255, 257.In other examples, fewer, additional, and/or different components may beprovided.

Examples of self-interference noise calculators described herein maygenerate and provide adjusted signals to compensation components. So,for example, the self-interference noise calculator 240 may generateadjusted signals y₁(n), y₂(n) 241, 243 and provide such adjusted signalsto the compensation components 245, 247. The self-interference noisecalculator 240 may generate such adjusted signals y₁(n), y₂(n) 241, 243based on transmitter output data x₁(n), x₂(n) 221, 223. Theself-interference noise calculator 240 may be in communication withmultiple (e.g. all) of the wireless transmitters of the electronicdevice 110 and all the respective compensation components coupled torespective wireless receivers, and may provide adjusted signals based ontransmitter output data.

It may be desirable in some examples to compensate for theself-interference noise to achieve full duplex transmission. Forexample, it may be desirable for wireless transmitters 111,113 of theelectronic device 110 to transmit wireless transmission signals at acertain frequency band; and, at the same time or simultaneously,wireless receivers 105, 107 receive wireless transmission signals onthat same frequency band. The self-interference noise calculator 240 maydetermine the self-interference contributed from each wirelesstransmission based on the transmitter output data to compensate eachreceived wireless transmission with an adjusted signal y₁(n), y₂(n) 241,243. Particularly as wireless communications move toward 5G standards,efficient use of wireless spectra may become increasingly important.

Examples of self-interference noise calculators described herein mayprovide the adjusted signals y₁(n), y₂(n) 241, 243 to receiver(s) and/ortransceiver(s). Compensation components 245, 247 may receive theadjusted signals y₁(n), y₂(n) 241, 243 and compensate an incomingreceived wireless transmission from antennas 105, 107. For example, thecompensation components 245, 247 may combine the adjusted signals withthe incoming received wireless transmission in a manner whichcompensates for (e.g. reduces) self-interference. In some examples, thecompensation components 245, 247 may subtract the adjusted signalsy₁(n), y₂(n) 241, 243 from the received wireless transmission to producecompensated received signals for the respective wireless receivers 115,117. The compensation components 245, 247 may communicate thecompensated received signals to the wireless receivers 115, 117. Thewireless receivers 115, 117 may process the compensated received signalwith the operations of a radio-frequency (RF) front-end. The wirelessreceiver may process the compensated received signals as a wirelessreceiver 400, for example. While the compensation components 245, 247have been described in terms of subtracting an adjusting signal from areceived wireless transmission, it can be appreciated that variouscompensations may be possible, such as adjusted signal that operates asa transfer function compensating the received wireless transmission oran adjusted signal that operates as an optimization vector to multiplythe received wireless transmission. Responsive to such compensation,electronic device 110 may transmit and receive wireless communicationssignals in a full duplex transmission mode.

Examples of self-interference noise calculators described herein,including the self-interference noise calculator 240 of FIG. 2 may beimplemented using hardware, software, firmware, or combinations thereof.For example, self-interference noise calculator 240 may be implementedusing circuitry and/or one or more processing unit(s) (e.g. processors)and memory encoded with executable instructions for causing theself-interference noise calculator to perform one or more functionsdescribed herein.

FIG. 3 is a schematic illustration of a wireless transmitter 300. Thewireless transmitter 300 receives a data signal 310 and performsoperations to generate wireless communication signals for transmissionvia the antenna 336. The wireless transmitter 300 may be utilized toimplement the electronic device 110 of FIG. 1 as a wireless transmitter,for example. The transmitter output data x_(N)(n) 310 is amplified by apower amplifier 332 before the output data are transmitted on an RFantenna 336. The operations to the RF-front end may generally beperformed with analog circuitry or processed as a digital basebandoperation for implementation of a digital front-end. The operations ofthe RF-front end. include a scrambler 304, a coder 308, an interleaver312, a modulation mapping 316, a frame adaptation 320, an IFFT 324, aguard interval 326, and frequency up-conversion 328.

The scrambler 304 may convert the input data to a pseudo-random orrandom binary sequence. For example, the input data may be a transportlayer source (such as MPEG-2 Transport stream and other data) that isconverted to a Pseudo Random Binary Sequence (PRBS) with a generatorpolynomial. While described in the example of a generator polynomial,various scramblers 304 are possible.

The coder 308 may encode the data outputted from the scrambler to codethe data. For example, a Reed-Solomon (RS) encoder, turbo encoder may beused as a first coder to generate a parity block for each randomizedtransport packet fed by the scrambler 304. In some examples, the lengthof parity block and the transport packet can vary according to variouswireless protocols. The interleaver 312 may interleave the parity blocksoutput by the coder 308, for example, the interleaver 312 may utilizeconvolutional byte interleaving. In some examples, additional coding andinterleaving can be performed after the coder 308 and interleaver 312.For example, additional coding may include a second coder that mayfurther code data output from the interleaver, for example, with apunctured convolutional coding having a certain constraint length.Additional interleaving may include an inner interleaver that formsgroups of joined blocks. While described in the context of a RS coding,turbo coding, and punctured convolution coding, various coders 308 arepossible, such as a low-density parity-check (LDPC) coder or a polarcoder. While described in the context of convolutional byteinterleaving, various interleavers 312 are possible.

The modulation mapping 316 may modulate the data output from theinterleaver 312. For example, quadrature amplitude modulation (QAM) maybe used to map the data by changing (e.g., modulating) the amplitude ofthe related carriers. Various modulation mappings may be used,including, but not limited to: Quadrature Phase Shift Keying (QPSK),SCMA NOMA, and MUSA (Multi-user Shared Access). Output from themodulation mapping 316 may be referred to as data symbols. Whiledescribed in the context of QAM modulation, various modulation mappings316 are possible. The frame adaptation 320 may arrange the output fromthe modulation mapping according to bit sequences that representcorresponding modulation symbols, carriers, and frames.

The IFFT 324 may transform symbols that have been framed intosub-carriers (e.g., by frame adaptation 320) into time-domain symbols.Taking an example of a 5G wireless protocol scheme, the IFFT can beapplied as N-point IFFT:

$\begin{matrix}{x_{k} = {\sum\limits_{n = 1}^{N}{X_{n}e^{i\; 2\; \pi \; {kn}\text{/}N}}}} & (1)\end{matrix}$

where Xn is the modulated symbol sent in the nth 5G sub-carrier.Accordingly, the output of the IFFT 324 may form time-domain 5G symbols.In some examples, the IFFT 324 may be replaced by a pulse shaping filteror poly-phase filtering banks to output symbols for frequencyup-conversion 328.

in the example of FIG. 3, the guard interval 326 adds a guard intervalto the time-domain 5G symbols. For example, the guard interval may be afractional length of a symbol duration that is added, to reduceinter-symbol interference, by repeating a portion of the end of atime-domain 5G symbol at the beginning of the frame. For example, theguard interval can be a time period corresponding to the cyclic prefixportion of the 5G wireless protocol scheme.

The frequency up-conversion 328 may up-convert the time-domain 5Gsymbols to a specific radio frequency. For example, the time-domain 5Gsymbols can be viewed as a baseband frequency range and a localoscillator can mix the frequency at which it oscillates with the 5Gsymbols to generate 5G symbols at the oscillation frequency: A digitalup-converter (DUC) may also be utilized to convert the time-domain 5Gsymbols. Accordingly, the 5G symbols can be up-converted to a specificradio frequency for an RF transmission.

Before transmission, at the antenna 336, a power amplifier 332 mayamplify the transmitter output data x_(N)(n) 310 to output data for anRF transmission in an RF domain at the antenna 336. The antenna 336 maybe an antenna designed to radiate at a specific radio frequency. Forexample, the antenna 336 may radiate at the frequency at which the 5Gsymbols were up-converted. Accordingly, the wireless transmitter 300 maytransmit an RF transmission via the antenna 336 based on the data signal310 received at the scrambler 304. As described above with respect toFIG. 3, the operations of the wireless transmitter 300 can include avariety of processing operations. Such operations can be implemented ina conventional wireless transmitter, with each operation implemented byspecifically-designed hardware for that respective operation. Forexample, a DSP processing unit may be specifically-designed to implementthe IFFT 324. As can be appreciated, additional operations of wirelesstransmitter 300 may be included in a conventional wireless receiver.

FIG. 4 is a schematic illustration of wireless receiver 400. Thewireless receiver 400 receives input data X (i,j) 410 from an antenna404 and performs operations of a wireless receiver to generate receiveroutput data at the descrambler 444. The wireless receiver 400 may beutilized to implement the electronic device 110 of FIG. 1 as a wirelessreceiver, for example. The antenna 404 may be an antenna designed toreceive at a specific radio frequency. The operations of the wirelessreceiver may be performed with analog circuitry or processed as adigital baseband operation for implementation of a digital front-end.The operations of the wireless receiver include a frequencydown-conversion 412, guard interval removal 416, a fast Fouriertransform 420, synchronization 424, channel estimation 428, ademodulation mapping 432, a deinterleaver 436, a decoder 440, and adescrambler 444.

The frequency down-conversion 412 may down-convert the frequency domainsymbols to a baseband processing range. For example, continuing in theexample of a 5G implementation, the frequency-domain 5G symbols may bemixed with a local oscillator frequency to generate 5G symbols at abaseband frequency range. A digital down-converter (DDC) may also beutilized to convert the frequency domain symbols. Accordingly, the RFtransmission including time-domain 5G symbols may be down-converted tobaseband. The guard interval removal 416 may remove a guard intervalfrom the frequency-domain 5G symbols. The FFT 420 may transform thetime-domain 5G symbols into frequency-domain 5G symbols. Taking anexample of a 5G wireless protocol scheme, the FFT can be applied asN-point FFT:

$\begin{matrix}{X_{n} = {\sum\limits_{k = 1}^{N}{x_{k}e^{{- i}\; 2\; \pi \; {kn}\text{/}N}}}} & (2)\end{matrix}$

where Xn is the modulated symbol sent in the nth 5G sub-carrier.Accordingly, the output of the FFT 420 may form frequency-domain 5Gsymbols. In some examples, the FFT 420 may be replaced by poly-phasefiltering banks to output symbols for synchronization 424.

The synchronization 424 may detect pilot symbols in the 5G symbols tosynchronize the transmitted data. In some examples of a 5Gimplementation, pilot symbols may be detected at the beginning of aframe (e.g., in a header) in the time-domain. Such symbols can be usedby the wireless receiver 400 for frame synchronization. With the framessynchronized, the 5G symbols proceed to channel estimation 428. Thechannel estimation 428 may also use the time-domain pilot symbols andadditional frequency-domain pilot symbols to estimate the time orfrequency effects (e.g., path loss) to the received signal.

For example, a channel may be estimated according to N signals receivedthrough N antennas (in addition to the antenna 404) in a preamble periodof each signal. In some examples, the channel estimation 428 may alsouse the guard interval that was removed at the guard interval removal416. With the channel estimate processing, the channel estimation 428may compensate for the frequency-domain 5G symbols by some factor tominimize the effects of the estimated channel. While channel estimationhas been described in terms of time-domain pilot symbols andfrequency-domain pilot symbols, other channel estimation techniques orsystems are possible, such as a MIMO-based channel estimation system ora frequency-domain equalization system.

The demodulation mapping 432 may demodulate the data outputted from thechannel estimation 428. For example, a quadrature amplitude modulation(QAM) demodulator can map the data by changing (e.g., modulating) theamplitude of the related carriers. Any modulation mapping describedherein can have a corresponding demodulation mapping as performed bydemodulation mapping 432. In some examples, the demodulation mapping 432may detect the phase of the carrier signal to facilitate thedemodulation of the 5G symbols. The demodulation mapping 432 maygenerate bit data from the 5G symbols to be further processed by thedeinterleaver 436.

The deinterleaver 436 may deinterleave the data bits, arranged as parityblock from demodulation mapping into a bit stream for the decoder 440,for example, the deinterleaver 436 may perform an inverse operation toconvolutional byte interleaving. The deinterleaver 436 may also use thechannel estimation to compensate for channel effects to the parityblocks.

The decoder 440 may decode the data outputted from the scrambler to codethe data. For example, a Reed-Solomon (RS) decoder or turbo decoder maybe used as a decoder to generate a decoded bit stream for thedescrambler 444. For example, a turbo decoder may implement a parallelconcatenated decoding scheme. In some examples, additional decodingand/or deinterleaving may be performed after the decoder 440 anddeinterleaver 436. For example, additional decoding may include anotherdecoder that may further decode data output from the decoder 440. Whiledescribed in the context of a RS decoding and turbo decoding, variousdecoders 440 are possible, such as low-density parity-check (LDPC)decoder or a polar decoder.

The descrambler 444 may convert the output data from decoder 440 from apseudo-random or random binary sequence to original source data. Forexample, the descrambler 44 may convert decoded data to a transportlayer destination e.g., MPEG-2 transport stream) that is descrambledwith an inverse to the generator polynomial of the scrambler 304. Thedescrambler thus outputs receiver output data. Accordingly, the wirelessreceiver 400 receives an RF transmission including input data X (i,j)410 via to generate the receiver output data.

As described herein, for example with respect to FIG. 4, the operationsof the wireless receiver 400 can include a variety of processingoperations. Such operations can be implemented in a conventionalwireless receiver, with each operation implemented byspecifically-designed hardware for that respective operation. Forexample, a DSP processing unit may be specifically-designed to implementthe FFT 420. As can be appreciated, additional operations of wirelessreceiver 400 may be included in a conventional wireless receiver.

FIG. 5A is a schematic illustration of an example self-interferencenoise calculator 500 arranged in accordance with examples describedherein. The self-interference noise calculator 500 may be utilized toimplement the self-interference noise calculator of FIG. 2 or theself-interference noise calculator 640 of FIG. 6, for example. Theself-interference noise calculator 500 may be referred to as a neuralnetwork, e.g., a neural network that calculates self-interference noise.The self-interference noise calculator 500 includes a network ofprocessing elements 504, 506, 509 that output adjusted signals y₁(n),y₂(n), y₃(n), y_(L)(n) 508 based on transmitter output data x₁(n),x₂(n), x₃(n), x_(N)(n) 502. For example, the transmitter output datax₁(n), x₂(n), x₃(n), x_(N)(n) 502 may correspond to inputs forrespective antennas of each transmitter generating the respective x₁(n),x₂(n), x₃(n), x_(N)(n) 502. The processing elements 504 receive thetransmitter output data x₁(n), x₂(n), x₃(n), x_(N)(n) 502. as inputs.The processing elements 504 may he implemented, for example, using bitmanipulation units that may forward the transmitter output data x₁(n),x₂(n), x₃(n), x_(N)(n) 502 to processing elements 506. Processingelements 506 may be implemented, for example, using multiplication unitsthat include a non-linear vector set (e.g., center vectors) based on anon-linear function, such as a Gaussian function

$\left( {{e.g.},{{\text{:}\mspace{14mu} {f(r)}} = {\exp \left( {- \frac{r^{2}}{\sigma^{2}}} \right)}},} \right.$

a multi-quadratic function (e.g., f(r)=(r²+σ²)), an inversemulti-quadratic function (e.g., f(r)=(r²σ²)), a thin-plate spinefunction (e.g., f(r)=r² log(r)), a piece-wise linear function (e.g.,f(r)=(|r+1|−|r−1|), or a cubic approximation function (e.g.,f(r)=1/2(|r³+1−|r³−1)). In some examples, the parameter a is a realparameter (e.g., a scaling parameter) and r is the distance between theinput signal (e.g., x₁(n), x₂(n), x₃(n), x_(N)(n) 502) and a vector ofthe non-linear vector set. Processing elements 509 may be implemented,for example, using accumulation units that sum the intermediateprocessing results received from each of the processing elements 506. Incommunicating the intermediate processing results, each intermediateprocessing result may be weighted with a weight ‘W’. For example, themultiplication processing units may weight the intermediate processingresults based on a minimized error for the all or some of the adjustmentsignals that may generated by a self-interference noise calculator.

The processing elements 506 include a non-linear vector set that may bedenoted as C_(i) (for i=1,2, . . . H). H may represent the number ofprocessing elements 506. With the transmitter output data x₁(n), x₂(n),x₃(n), x_(N)(n) 502 received as inputs to processing elements 506, afterforwarding by processing elements 504, the output of the processingelements 506, operating as multiplication processing units, may beexpressed as h_(i)(n), such that:

h _(i)(n)=f _(i)(∥X(n)−C _(i)∥) (i=1,2, . . . , H)   (3)

f_(i) may represent a non-linear function that is applied to themagnitude of the difference between x₁(n), x₂(n), x₃(n), x_(N)(n) 502and the center vectors C_(i). The output h_(i)(n) may represent anon-linear function such as a Gaussian function, multi-quadraticfunction, an inverse multi-quadratic function, a thin-plate spinefunction, or a cubic approximation function.

The output h_(i)(n) of the processing elements 506 may be weighted witha weight matrix ‘W’. The output h_(i)(n) of the processing elements 506can be referred to as intermediate processing results of theself-interference noise calculator 500. For example, the connectionbetween the processing elements 506 and processing elements 509 may be alinear function such that the summation of a weighted output h_(i)(n)such that the adjusted signals y₁(n), y₂(n), y₃(n), y_(L)(n) 508 may beexpressed, in Equation 4 as:

y _(i)(n)=τ_(j=1) ^(H) W _(ij) h _(j)(n)=τ_(j=1) ^(H) W _(ij) f_(j)(∥X(n)−C _(j)∥) (i=1,2, . . . , L)   (4)

Accordingly, the adjusted signals y₁(n), y₂(n), y₃(n), yL(n) 508 may bethe output vi(i0 of the i'th processing element 509 at time n, where Lis the number of processing elements 509. W_(ij) is the connectionweight between j'th processing element 506 and i'th processing element509 in the output layer. As described with respect to FIG. 6, the centervectors C_(i) and the connection weights W_(ij) of each layer ofprocessing elements may be determined by a training unit 650 thatutilizes sample vectors 660 to train a self-interference calculator 640.Advantageously, the adjusted signals y₁(n), y₂(n), y₃(n), y_(L)(n) 508generated from the transmitter output data x₁(n), x₂(n), x₃(n), x_(N)(n)502 may be computed with near-zero latency such that self-interferencecompensation may be achieved in any electronic device including aself-interference noise calculator, such as the self-interference noisecalculator 500. A wireless device or system that implements aself-interference noise calculator 500 may achieve full duplextransmission. For example, the adjusted signals generated by theinterference noise calculator 500 may compensate-interference that anantenna of the wireless device or system will experience due totransmission signals (e.g., transmitter output data) by another antennaof the wireless device or system.

While the self-interference noise calculator 500 has been described withrespect to a single layer of processing elements 506 that includemultiplication units, it can be appreciated that additional layers ofprocessing elements with multiplication units may be added between theprocessing elements 504 and the processing elements 509. Theself-interference noise calculator is scalable in hardware form, withadditional multiplication units being added to accommodate additionallayers. Using the methods and systems described herein, additionallayer(s) of processing elements including multiplication processingunits and the processing elements 506 may be optimized to determine thecenter vectors C_(i) and the connection weights W_(ij) of each layer ofprocessing elements including multiplication units. In someimplementations, for example as described with reference to FIGS. 5C-5E,layers of processing elements 506 may includemultiplication/accumulation (MAC) units, with each layer havingadditional MAC units. Such implementations, having accumulated theintermediate processing results in a respective processing elements(e.g., the respective MAC unit), may also include memory look-up (MLU)units that are configured to retrieve a plurality of coefficients andprovide the plurality of coefficients as the connection weights for therespective layer of processing elements 506 to be mixed with the inputdata.

The self-interference noise calculator 500 can be implemented using oneor more processors, for example, having any number of cores. An exampleprocessor core can include an arithmetic logic unit (ALU), a bitmanipulation unit, a multiplication unit, an accumulation unit, amultiplication/accumulation (MAC) unit, an adder unit, a look-up tableunit, a memory look-up unit, or any combination thereof. In someexamples, the self-interference noise calculator 240 may includecircuitry, including custom circuitry, and/or firmware for performingfunctions described herein, For example, circuitry can includemultiplication unit, accumulation units, MAC units, and/or bitmanipulation units for performing the described functions, as describedherein. The self-interference noise calculator 240 may be implemented inany type of processor architecture including but not limited to amicroprocessor or a digital signal processor (DSP), or any combinationthereof.

FIG. 5B is a schematic illustration of a recurrent neural networkarranged in accordance with examples described herein. The recurrentneural network 170 include three stages (e.g., layers): an inputs stage171; a combiner stage 173 and 175, and an outputs stage 177. While threestages are shown in FIG. 5B, any number of stages may be used in otherexamples, e.g., as described with reference to FIGS. 5C-5E. In someimplementations, the recurrent neural network 170 may have multiplecombiner stages such that outputs from one combiner stage is provided toanother combiners stage, until being providing to an outputs stage 177.As described with reference to FIG. 5C, for example, there may bemultiple combiner stages in a neural network 170. As depicted in FIG.5B, the delay units 175 a, 175 b, and 175 c may be optional componentsof the neural network 170. When such delay units 175 a, 175 b, and 175 care utilized as described herein, the neural network 170 may be referredto as a recurrent neural network.

The first stage of the neural network 170 includes inputs node 171. Theinputs node 171 may receive input data at various inputs of therecurrent neural network. The second stage of the neural network 170 isa combiner stage including combiner units 173 a, 173 b, 173 c; and delayunits 175 a, 175 b, 175 c. Accordingly, the combiner units 173 and delayunits 175 may be collectively referred to as a stage of combiners.Accordingly, as described with respect to FIG. 5C with processing units512 implementing such combiners, generally processing units 512 thatimplement the combiner units 173 a-c and delay units 175 a-c in thesecond stage may perform a nonlinear activation function using the inputdata from the inputs node 171 (e.g., input signals X1(n), X2(n), andX3(n)). The third stage of neural network 170 includes the outputs node177, Additional, fewer, and/or different components may be used in otherexamples. As described with analogous elements of the self-interferencenoise calculator 500 of FIG. 5A, the recurrent neural network 170 mayalso implement a self-interference noise calculator, as described withrespect to the processing units 512 of FIGS. 5C-5E that may calculateself-interference noise, implementing a recurrent neural network 170. Assuch, the implementations of FIGS. 5C-5E may be referred to as recurrentself-interference noise calculators.

The recurrent neural network 170 includes delay units 175 a, 175 b, and175 c, which generate delayed versions of the output from the respectivecombiner units 173 a-c based on receiving such output data from therespective combiner units 173 a-c. In the example, the output data ofcombiner units 173 a-c may be represented as h(n); and, accordingly,each of the delay units 175 a-c delay the output data of the combinerunits 173 a-c to generate delayed versions of the output data from thecombiner units 173 a-c, which may be represented as h(n-t). In variousimplementations, the amount of the delay, t, may also vary, e.g., oneclock cycle, two clock cycles, or one hundred clock cycles. That is, thedelay unit 175 may receive a clock signal and utilize the clock signalto identify the amount of the delay. In the example of FIG. 5B, thedelayed versions are delayed by one time period, where ‘1’ represents atime period. A time period may corresponds to any number of units oftime, such as a time period defined by a clock signal or a time perioddefined by another element of the neural network 170.

Continuing in the example of FIG. 5B, each delay unit 175 a-c providesthe delayed versions of the output data from the combiner units 173 a-cas input to the combiner units 173 a-c, to operate, optionally, as arecurrent neural network. Such delay units 175 a-c may providerespective delayed versions of the output data from nodes of thecombiner units 173 a-c to respective input units/nodes of the combinerunits 173 a-c. In utilizing delayed versions of output data fromcombiner units 173 a-c, the recurrent neural network 170 may trainweights at the combiner units 173 a-c that incorporate time-varyingaspects of input data to be processed by such a recurrent neural network170. Once trained, in some examples, the inputs node 171 receiveswireless input data that is to be received and processed in therecurrent neural network 170 as a wireless receiver associated with awireless protocol. Each stream of input data may correspond to a signalto be transmitted (e.g., the transmitter output data) at correspondingantennas (e.g., antennas 101 and 103 FIG. 1). Accordingly, because anRNN 170 incorporates the delayed versions of output data from combinerunits 173 a-c, the time-varying nature of the input data may providefaster and more efficient processing of the input data.

Generally, a recurrent neural network may include multiple stages ofnodes. The nodes may be implemented using processing units (e.g.,processing units 512) which may execute one or more functions on inputsreceived from a previous stage and provide the output of the functionsto the next stage of the recurrent neural network. The processing unitsmay be implemented using, for example, one or more processors,controllers, and/or custom circuitry, such as an application specificintegrated circuit (ASIC) and/or a field programmable gate array (FPGA).In some examples, the processing units may be implemented using anycombination of one or more processing units 512 described with respectto FIGS. 5C-5E. The processing units may be implemented as combinersand/or summers and/or any other structure for performing functionsallocated to the processing unit. In some examples, certain of theelements of neural networks described herein perform weighted sums,e.g., may be implemented using one or more multiplication/accumulationunits, which may be implemented using processor(s) and/or othercircuitry. In an example, the neural network 170 may be implemented bythe electronic device 110 utilizing any combination of one or moreprocessing units described with respect to FIGS. 5C-5E.

Examples of recurrent neural network training and inference can bedescribed mathematically. Again, as an example, consider input data at atime instant (n), given as: X(n)=[x₁(n), x₂(n), . . . x_(m)(n)]^(r). Thecenter vector for each element in hidden layer(s) of the recurrentneural network 170 (e.g., combiner units 173 a-c) may be denoted asC_(i)(for i=1, 2, . . . , H, where H is the element number in the hiddenlayer).

The output of each element in a hidden layer may then be given as:

h _(i)(n)=f _(i)(∥X(n)+h _(i)(−t)−C _(i)∥) for (i=1,2, . . . , H)   (5)

i may be the delay at the delay unit 175 such that the output of thecombiner units 173 includes a delayed version of the output of thecombiner units 173. In some examples, this may be referred to asfeedback of the combiner units 173. Accordingly, each of the connectionsbetween a last hidden layer and the output layer may be weighted. Eachelement in the output layer may have a linear input-output relationshipsuch that it may perform a summation (e.g., a weighted summation).Accordingly, an output of the i'th element in the output layer at time nmay be written as:

$\begin{matrix}\begin{matrix}{{y_{i}(n)} = {{\sum_{j = 1}^{H}{W_{ij}{h_{j}(n)}}} + {W_{ij}{h_{j}\left( {n - t} \right)}}}} \\{= {\sum_{j = 1}^{H}{W_{ij}{f_{j}\left( {{{X(n)} + {h_{i}\left( {n - t} \right)} - C_{j}}} \right)}}}}\end{matrix} & (6)\end{matrix}$

for (i=1, 2, . . . , L) and where L is the element number of the outputof the output layer and is the connection weight between the j'thelement in the hidden layer and the i'th element in the output layer.

Additionally or alternatively, while FIG. 5B has been described withrespect to a single stage of combiners (e.g,, second stage) includingthe combiner units 173 a-c and delay units 175 a-c, it can beappreciated that multiple stages of similar combiner stages may beincluded in the neural network 170 with varying types of combiner unitsand varying types of delay units with varying delays, for example, aswill now be described with reference to FIGS. 5C-5E.

FIG. 5C is a schematic illustration of a processing unit 512 arranged ina system 501 in accordance with examples described herein. Such ahardware implementation (e.g., system 501) may be used, for example, toimplement one or more neural networks, such as the self-interferencenoise calculator 240 of FIG. 2, self-interference noise calculator 500of FIG. 5A or recurrent neural network 170 of FIG. 5B. Additionally oralternatively, in some implementations, the processing unit 512 mayreceive input data 510 a, 510 b, and 510 c from such a computing system.The input data 510 a, 510 b, and 510 c may be data to be transmitted,which may be stored in a memory 545. In some examples, data stored inthe memory 545 may be input data to be transmitted from a plurality ofantennas coupled to an electronic device 110 in which the processingunit 512 is implemented. In an example in which the electronic device110 is coupled to the plurality of antennas 101 and 103, the input data510 a. X₁(i, i−1) may correspond to a first RE transmission to betransmitted at the antenna 101 at a first frequency; the input data 510b X₂(i, i−1) may correspond to a second RF transmission to betransmitted at the antenna 103 at a second frequency; and the input data510 c X_(m)(i, i−1) may correspond to a m'th RF transmission to betransmitted at an m'th antenna at a m'th frequency. in may represent thenumber of antennas, with each antenna transmitting a portion of inputdata.

In some examples, m may also correspond to a number of wireless channelsover which the input data is to be transmitted; for example, in a MIMOtransmission, an RF transmission may be sent over multiple wirelesschannels at the plurality of antennas 101 and 103. In an example of theinput data being received (in contrast to being transmitted), the inputdata 510 a, 510 b, 510 c may corresponds to portions of input data to beprocessed as an RF transmission received at multiple antennas. Forexample, the output data 530 B(1) may be a MIMO output signal receivedat the antennas 101 and 103 at an electronic device that is implementingthe processing unit 512 of the computing system 501. As denoted in therepresentation of the input data signals, the input data 510 a X₁(i,i−1) includes a current portion of the input data, at time i, and aprevious portion of the input data, at time i−1. For example, a currentportion of the input data may be a sample obtained at the antenna 101 ata certain time period (e.g., at time i), while a previous portion of theinput data may be a sample obtained at the antenna 101 at a time periodprevious to the certain time period (e.g., at time i−1). Accordingly,the previous portion of the input data may be referred to as atime-delayed version of the current portion of the input data. Theportions of the input data at each time period may be obtained in avector or matrix format, for example. In an example, a current portionof the input data, at time i, may be a single value; and a previousportion of the input data, at time i−1, may be a single value. Thus, theinput data 510 a X₁(i, i−1) may be a vector, in some examples, thecurrent portion of the input data, at time i, may be a vector value; anda previous portion of the input data, at time i−1, may be a vectorvalue. Thus, the input data 510 a X₁(i, i−1) may be a matrix.

Such input data, which is obtained with a current and previous portionof input data, may be representative of a Markov process, such that acausal relationship between at least the current sample and the previoussample may improve the accuracy of weight estimation for training ofcoefficient data to be utilized by the MAC units and MLUs of theprocessing unit 512. As noted previously, the input data 510 mayrepresent data to be transmitted (e.g., transmitter output data) at afirst frequency and/or data to be transmitted at a first wirelesschannel. Accordingly, the input data 510 b X₂(i, i−1) may represent datato be transmitted at a second frequency or at a second wireless channel,including a current portion of the input data, at time i, and a previousportion of the input data, at time i−1. And, the number of input signalsto be transmitted by the processing unit 512 may equal in some examplesto a number of antennas coupled to an electronic device 110 implementingthe processing unit 512. Accordingly, the input data 510 c X_(m)(i, i−1)may represent data to be transmitted at a m'th frequency or at a m'thwireless channel, including a current portion of the input data, at timei, and a previous portion of the input data, at time i−1.

The processing unit 512 may include multiplication unit/accumulation(MAC) units 511 a-c, 516 a-b, and 520; delay units 513 a-c, 517 a-b, and521; and memory lookup units (MLUs) 514 a-c, 518 a-b, and 522 that, whenmixed with input data to be transmitted from the memory 545, maygenerate output data (e.g. B (1)) 530. Each set of MAC units and MLUunits having different element numbers may be referred to as arespective stage of combiners for the processing unit 512. For example,a first stage of combiners includes MAC units 511 a-c and MLUs 514 a-c,operating in conjunction with delay units 513 a-c, to form a first stageor “layer,” as referenced with respect to FIG. 5A having “hidden” layersas various combiner stages. Continuing in the example, the second stageof combiners includes MAC units 516 a-b and MLUs 518 a-b, operating inconjunction with delay units 517 a-b, to form a second stage or secondlayer of hidden layers. And the third stage of combiners may be a singlecombiner including the MAC unit 520 and MLU 522, operating inconjunction with delay unit 521, to form a third stage or third layer ofhidden layers.

In an example of generating RF transmission for transmission, the outputdata 530 B(1) may be utilized as a MIMO RF signal to be transmitted at aplurality of antennas. In an example of obtaining RF transmission thatwere obtained at a plurality of antennas, the output data 530 B(1) mayrepresentative of a demodulated, decoded signal that was transmitted byanother RF electronic device. In any case, the processing unit 512, maybe provide instructions 515, stored at the mode configurable control505. to cause the processing unit 512 to configure the multiplicationunits 511 a-c, 516 a-c, and 520 to multiply and/or accumulate input data510 a, 510 b, and 510 c and delayed versions of processing results fromthe delay units 513 a-c, 517 a-b, and 521 (e.g., respective outputs ofthe respective layers of MAC units) with coefficient data to generatethe output data 530 B(1). For example, the mode configurable control 505may execute instructions that cause the memory 545 to provide weightsand/or other parameters stored in the memory 545, which may beassociated. with a certain wireless processing mode, to the MLUs 514a-c, 518 a-b, and 522 as weights for the MAC units 511 a-c, 516 a-b, and520 and delay units 513 a-c, 517 a-b, and 521. During operation, themode configuration control 505 may be used to select weights and/orother parameters in memory 545 based on an indicated self-interferencenoise to calculate, e.g., the self-interference noise from a certaintransmitting antenna to another transmitting antenna.

As denoted in the representation of the respective outputs of therespective layers of MAC units (e.g., the outputs of the MLUs 514 a-c,518 a-b, and 522), the input data to each MAC unit 511 a-c, 516 a-b, and520 includes a current portion of input data, at time i, and a delayedversion of a processing result, at time i−1. For example, a currentportion of the input data may be a sample obtained at the antenna 101 ata certain time period (e.g., at time i), while a delayed version of aprocessing result may be obtained from the output of the delay units 513a-c, 517 a-b, and 521, which is representative of a time period previousto the certain time period (e.g., as a result of the introduced delay).Accordingly, in using such input data, obtained from both a currentperiod and at least one previous period, output data B(1) 530 may berepresentative of a Markov process, such that a causal relationshipbetween at least data from a current time period and a previous timeperiod may improve the accuracy of weight estimation for training ofcoefficient data to be utilized by the MAC units and MLUs of theprocessing unit 512 or inference of signals to be transmitted inutilizing the processing unit 512. As noted previously, the input data510 may represent transmitter output data x₁(n), x₂(n) 221, 223.Accordingly, the input data 510 b X2(i, i−1) may represent transmitteroutput data x₂(n) 223. And, the number of input signals obtained by theprocessing unit 512 may equal in some examples to a number of antennascoupled to an electronic device 110 implementing the processing unit512. Accordingly, the input data 510 c Xm(i, i−1) may represent dataobtained at a m'th frequency or at a m'th wireless channel, including acurrent portion of the input data, at time i. Accordingly, in utilizingdelayed versions of output data from 513 a-c, 517 a-b, and 521 therecurrent neural network 170 provides individualized frequency-band,time-correlation data for processing of signals to be transmitted.

In an example of executing such instructions 515 for mixing input datawith coefficients, at a first layer of the MAC units 511 a-c and MLUs514 a-c, the multiplication unit/accumulation units 511 a-c areconfigured to multiply and accumulate at least two operands fromcorresponding input data 510 a, 510 b, or 510 c and an operand from arespective delay unit 513 a-c to generate a multiplication processingresult that is provided to the MLUs 514 a-c. For example, themultiplication unit/accumulation units 511 a-c may perform amultiply-accumulate operation such that three operands, M N, and T aremultiplied and then added with to generate a new version of P that isstored in its respective MLU 514 a-c. Accordingly, the MLU 514 a latchesthe multiplication processing result, until such time that the storedmultiplication processing result is be provided to a next layer of MACunits. The MLUs 514 a-c, 518 a-b, and 522 may be implemented by anynumber of processing elements that operate as a memory look-up unit suchas a D, T, SR, and/or JK latches.

The MLUs 514 a-c, 518 a-b, and 522 shown in FIG. 5C may generallyperform a predetermined nonlinear mapping from input to output. Forexample, the MLUs 514 a-c, 518 a-b, and 522 may be used to evaluate atleast one non-linear function. In some examples, the contents and sizeof the various MLUs 514 a-c, 518 a-b, and 522 depicted may be differentand may be predetermined. In some examples, one or more of the MLUs 514a-c, 518 a-b, and 522 shown in FIG. 5C may be replaced by a singleconsolidated MLU (e.g., a table look-up). Examples of nonlinear mappings(e.g., functions) which may be performed by the MLUs 514 a-c, 518 a-b,and 522 include Gaussian functions, piece-wise linear functions, sigmoid functions, thin-plate-spline functions, multi-quadratic functions,cubic approximations, and inverse multi-quadratic functions. Examples offunctions have been described with reference also to FIG. 5A. In someexamples, selected MLUs 514 a-c, 518 a-b, and 522 may be by-passedand/or may be de-activated, which may allow an MLU and its associatedMAC unit to be considered a unity gain element.

Additionally in the example, the MLU 514 a provides the processingresult to the delay unit 513 a. The delay unit 513 a delays theprocessing result (e.g., h1(i)) to generate a delayed version of theprocessing result (e.g, h1(i−1)) to output to the MAC unit 511 a asoperand T. While the delay units 513 a-c, 517 a-b, and 521 of FIG. 5Care depicted introducing a delay of ‘1’, it can be appreciated thatvarying amounts of delay may be introduced to the outputs of first layerof MAC units. For example, a clock signal that introduced a sample delayof ‘1’ (e.g., h1(i−1)) may instead introduce a sample delay of ‘2’, ‘4’,or ‘100’. In various implementations, the delay units 513 a-c, 517 a-b,and 521 may correspond to any number of processing units that canintroduce a delay into processing circuitry using a clock signal orother time-oriented signal, such as flops (e.g., D-flops) and/or one ormore various logic gates (e.g., AND, OR, NOR, etc . . . ) that mayoperate as a delay unit.

In the example of a first hidden layer of a recurrent neural network,the MLUs 514 a-c may retrieve coefficient data stored in the memory 545,which may he weights associated with weights to be applied to the firstlayer of MAC units to both the data from the current period and datafrom a previous period (e.g., the delayed versions of first layerprocessing results). For example, the MLU 514 a can be a table look-upthat retrieves one or more coefficients (e.g., specific coefficientsassociated with a first frequency) to be applied to both operands M andN, as well as an additional coefficient to be applied to operand T. TheMLUs 514 a-c also provide the generated multiplication processingresults to the next layer of the MAC units 516 a-b and MLUs 518 a-b. Theadditional layers of the MAC units 516 a, 516 b and MAC unit 520 workingin conjunction with the MLUs 518 a, 518 b and MLU 522, respectively, maycontinue to process the multiplication results to generate the outputdata 530 B(n). Using such a circuitry arrangement, the output data 530B(1) may be generated from the input data 510 a, 510 b, and 510 c.

Advantageously, the processing unit 512 of system 501 may utilize areduced number of MAC units and/or Mills, e.g., as compared to theprocessing unit 512 of FIG. 5D. The number of MAC units and MLUs in eachlayer of the processing unit 512 is associated with a number of channelsand/or a number of antennas coupled to a device in which the processingunit 512 is being implemented. For example, the first layer of the MACunits and MLUs may include in number of those units, where m representsthe number of antennas, each antenna receiving a portion of input data.Each subsequent layer may have a reduced portion of MAC units, delayunits, and MLUs. As depicted, in FIG. 5C for example, a second layer ofMAC units 516 a-b, delay unit 517 a-b, and MLUs 518 a-b may include m−1MAC units and MLUs, when m=3. Accordingly, the last layer in theprocessing unit 512, including the MAC unit 520, delay unit 521, and MLU522, includes only one MAC, one delay unit, and one MLU. Because theprocessing unit 512 utilizes input data 510 a, 510 b, and 510 c that mayrepresent a Markov process, the number of MAC units and MLUs in eachsubsequent layer of the processing unit may be reduced, without asubstantial loss in precision as to the output data 530 B(1); forexample, when compared to a processing unit 512 that includes the samenumber of MAC units and MLUs in each layer, like that of processing unit512 of system 550.

The coefficient data, for example from memory 545, can be mixed with theinput data 510 a-510 c and delayed version of processing results togenerate the output data 530 B(1). For example, the relationship of thecoefficient data to the output data 530 B(1) based on the input data 510a-c and the delayed versions of processing results may be expressed as:

B(1)=α¹ *f(Σ_(j=1) ^(m−1)α^((m−1)) f _(j)(Σ_(k=1) ^(m)α^((m)) X_(k)(i)))   (7)

where a(m), a(m−1), a1 are coefficients for the first layer ofmultiplication/accumulation units 511 a-c and outputs of delay units 513a-c; the second layer of multiplication/accumulation units 516 a-b andoutputs of delay units 517 a-b; and last layer with themultiplication/accumulation unit 520 and output of delay unit 521,respectively; and where f(•) is the mapping relationship which may beperformed by the memory look-up units 514 a-c and 518 a-b. As describedabove, the memory look-up units 514 a-c and 518 a-b retrievecoefficients to mix with the input data and respective delayed versionsof each layer of MAC units. Accordingly, the output data may be providedby manipulating the input data and delayed versions of the MAC unitswith the respective multiplication/accumulation units using a set ofcoefficients stored in the memory. The set of coefficients may beassociated with vectors representative of self-interference noise. Forexample, in the case of signals to be transmitted, each coefficient of aset of coefficients may be an individual vector of self-interference ofa respective wireless path to a first transmitting antenna of theplurality of antennas from at least one other transmitting antenna ofthe plurality of transmitting antennas. The set of coefficients may bebased on connection weights obtained from the training of a recurrentneural network (e.g., recurrent neural network 170). The resultingmapped data may be manipulated by additional multiplication/accumulationunits and additional delay units using additional sets of coefficientsstored in the memory associated with the desired wireless protocol. Thesets of coefficients multiplied at each stage of the processing unit 512may represent or provide an estimation of the processing of the inputdata in specifically-designed hardware (e.g., an FPGA).

Further, it can be shown that the system 501, as represented by Equation(7), may approximate any nonlinear mapping with arbitrarily small errorin some examples and the mapping of system 501 may be determined by thecoefficients a(m), a(m−1), a1. For example, if such coefficient data isspecified, any mapping and processing between the input data 510 a-510 cand the output data 530 may be accomplished by the system 501. Forexample, the coefficient data may represent non-linear mappings of theinput data 510 a-c to the output data B(1) 530. In some examples, thenon-linear mappings of the coefficient data may represent a Gaussianfunction, a piece-wise linear function, a sigmoid function, athin-plate-spline function, a multi-quadratic function, a cubicapproximation, an inverse multi-quadratic function, or combinationsthereof. In some examples, some or all of the memory look-up units 514a-c, 518 a-b may be deactivated. For example, one or more of the memorylook-up units 514 a-c, 518 a-b may operate as a gain unit with the unitygain. Such a relationship, as derived from the circuitry arrangementdepicted in system 501, may be used to train an entity of the computingsystem 501 to generate coefficient data. For example, using Equation(7), an entity of the computing system 501 may compare input data to theoutput data to generate the coefficient data.

Each of the multiplication unit/accumulation units 511 a-c, 516 a-b, and520 may include multiple multipliers, multiple accumulation unit, orand/or multiple adders. Any one of the multiplication unit/accumulationunits 511 a-c, 516 a-b, and 520 may be implemented using an ALU. In someexamples, any one of the multiplication unit/accumulation units 511 a-c,516 a-b, and 520 can include one multiplier and one adder that eachperform, respectively, multiple multiplications and multiple additions.The input-output relationship of a multiplication/accumulation unit 511a-c, 516 a-b, and 520 may be represented as:

$\begin{matrix}{B_{out} = {\sum\limits_{i = 1}^{I}{C_{i}*{B_{in}(i)}}}} & (8)\end{matrix}$

where “I” represents a number to perform the multiplications in thatunit, C_(i) the coefficients which may be accessed from a memory, suchas memory 545, and B_(in)(i) represents a factor from either the inputdata 510 a-c or an output from multiplication unit/accumulation units511 a-c, 516 a-b, and 520. In an example, the output of a set ofmultiplication unit/accumulation units, B_(out), equals the sum ofcoefficient data, C_(i) multiplied by the output of another set ofmultiplication unit/accumulation units, B_(in)(i). B_(in)(i) may also bethe input data such that the output of a set of multiplicationunit/accumulation units, B_(out), equals the sum of coefficient data,C_(i) multiplied by input data.

While described in FIG. 5C as a processing unit 512, it can beappreciated that the processing unit 512 may be implemented in or as anyof the self-interference noise calculators described herein, inoperation to cancel and/or compensate self-interference noise via thecalculation of such noise as implemented in a recurrent neural network.In such implementations, recurrent neural networks may be used to reduceand/or improve errors which may be introduced by self-interferencenoise. Advantageously, with such an implementation, wireless systems anddevices implementing such RNNs increase capacity of their respectivewireless networks because additional data may be transmitted in suchnetworks, which would not otherwise be transmitted due to the effects ofself-interference noise.

FIG. 5D is a schematic illustration of a processing unit 512 arranged ina system 550 in accordance with examples described herein. Such ahardware implementation (e.g., system 550) may be used, for example, toimplement one or more neural networks, such as the self-interferencenoise calculator 240 of FIG. 2, self-interference noise calculator 500of FIG. 5A, or recurrent neural network 170 of FIG. 5B. Similarlydescribed elements of FIG. 5D may operate as described with respect toFIG. 5C, but may also include additional features as described withrespect to FIG. 5D. For example, FIG. 5D depicts MAC units 562 a-c anddelay units 563 a-c that may operate as described with respect MAC units511 a-c and delay units 513 a-c of FIG. 5C. Accordingly, elements ofFIG. 5D, whose numerical indicator is offset by 50 with respect to FIG.5C, include similarly elements of the processing element 512; e.g., MACunit 566 a operates similarly with respect to MAC unit 516 a. The system550, including processing element 512, also includes additional featuresnot highlighted in the processing element 512 of FIG. 5C. For example,the processing unit 512 of FIG. 5D additionally includes MAC units 566 cand 570 b-c; delay units 567 c and 571 b-c; and MLUs 568 c and 572 b-c,such that the output data is provided as 575 a-c, rather than assingularly in FIG. 5C as B(1) 530. Advantageously, the system 550including a processing element 512 may process the input data 560 a-c togenerate the output data 575 a-c with greater precision. For example,the output data 575 a-c may process the input data 560 a-560 c withadditional coefficient retrieved at MLU 568 c and multiplied and/oraccumulated by additional MAC units 566 c and 570 b-c and additionaldelay units 567 c and 571 b-c. For example, such additional processingmay result in output data that is more precise with respect providingoutput data that estimates a vector representative of self-interferencenoise between two different antennas. In implementations where boardspace (e.g., a printed circuit board) is not a primary factor in design,implementations of the processing unit 512 of FIG. 5D may be desirableas compared to that of processing unit 512 of FIG. 5C; which, in someimplementations may occupy less board space as a result of having fewerelements than the processing unit 512 of FIG. 5D.

Additionally or alternatively, the processing unit 512 of system 550 mayalso be utilized for applications in which each portion of the outputdata 575 a-c is to be transmitted as a MIMO signal on a correspondingantenna. For example, the output data 575 a may be transmitted as aportion of a MIMO transmission at a first antenna having a firstfrequency; the output data 575 b may be transmitted as a second portionof a MIMO transmission at a second antenna having a second frequency;and the output data 575 c may be transmitted as a n'th portion of thetransmission at a n'th antenna having an n'th frequency.

FIG. 5E is a schematic illustration of a processing unit 512 arranged ina system 580 in accordance with examples described herein. Such ahardware implementation (e.g., system 580) may be used, for example, toimplement one or more neural networks, such as the self-interferencenoise calculator 240 of FIG. 2, self-interference noise calculator 500of FIG. 5A, or recurrent neural network 170 of FIG. 5B. Similarlydescribed elements of FIG. 5E may operate as described with respect toFIG. 5D, except for the delay units 563 a-c, 567 a-c, and 571 a-c ofFIG. 5D. For example, FIG. 5E depicts MAC units 582 a-c and delay units583 a-c that may operate as described with respect to MAC units 562 a-cand delay units 563 a-c of FIG. 5D, Accordingly, elements of FIG. 5E,whose numerical indicator is offset by 20 with respect to FIG. 5D,include similarly elements of the processing element 512; e.g., MAC unit586 a operates similarly with respect to MAC unit 566 a.

The system 580, including processing element 512, also includesadditional features not highlighted in the processing element 512 ofFIG. 5D. Different than FIG. 5D, FIG. 5E depicts delay units 583 a, 583b, and 583 c. Accordingly, the processing unit of FIG. 5E illustratethat processing units 512 may include varying arrangements to theplacement of the inputs and outputs of delay units, as illustrated withdelay units 583 a, 583 b, and 583 c. For example, the output of MLUs 588b may be provided to delay unit 583 b, to generate a delayed version ofthat processing result from the second layer of MAC units, as an inputto the first layer of MAC units, e.g., as an input to MAC unit 582 b.Accordingly, the processing unit 512 of system 580 is illustrative thatdelayed versions of processing results may be provided as inputs toother hidden layers, different than the processing unit 512 of system550 in FIG. 5D showing respective delayed versions being provided asinputs to the same layer in which those delayed versions were generated(e.g., the output of MLU 568 b is provided to delay unit 567 b, togenerate a delayed version for the MAC unit 566 b in the same layer fromwhich the processing result was outputted). Therefore, in the example,even the output B(n) 595 c may be provided, from the last hidden layer,to the first hidden layer (e.g., as an input to MAC unit 582 c).

Advantageously, such delayed versions of processing results, which maybe provided as inputs to different or additional hidden layers, maybetter compensate “higher-order” memory effects in a recurrent neuralnetwork 170 that implements one or more processing units 512 of FIG. 5E,e.g., as compared to the processing unit(s) 512 of FIGS. 5C or 5D. Forexample, higher-order memory effects model the effects of leading andlagging envelope signals used during training of the recurrent neuralnetwork 170, to provide output data that estimates a vectorrepresentative of self-interference noise between two different antennasof an electronic device 110. In the example, a recurrent neural network170 that estimates that vector (e.g., a Volterra series model) mayinclude varying delayed versions of processing results that correspondsto such leading and lagging envelopes (e.g., of various envelopesencapsulating the vector). Accordingly, implementing the processing unit512 incorporates such higher-order memory effects, e.g., for aninference of a recurrent neural network 170, to provide output data 595a-c based on input data 581 a-c.

Additionally or alternatively, the processing unit 512 of system 580 mayalso be utilized for applications in which each portion of the outputdata 595 a-c is to be transmitted as a MIMO signal on a correspondingantenna. For example, the output data 595 a may be transmitted as aportion of a MIMO transmission at a first antenna having a firstfrequency; the output data 595 b may be transmitted as a second portionof a MIMO transmission at a second antenna having a second frequency;and the output data 595 c may be transmitted as a n'th portion of theMIMO transmission at a n'th antenna having an n'th frequency.

While described in FIGS. 5D and SE respectively describe a processingunit 512, it can be appreciated that the processing unit 512 orcombinations thereof may be implemented in or as any of theself-interference noise calculators described herein, in operation tocancel and/or compensate self-interference noise via the calculation ofsuch noise as implemented in a recurrent neural network. In suchimplementations, recurrent neural networks may be used to reduce and/orimprove errors which may be introduced by self-interference noise.Advantageously, with such an implementation, wireless systems anddevices implementing such RNNs increase capacity of their respectivewireless networks because additional data may be transmitted in suchnetworks, which would not otherwise be transmitted due to the effects ofself-interference noise.

FIG. 6 is a schematic illustration 600 of an electronic device 610arranged in accordance with examples described herein. The electronicdevice 610 includes antennas 101, 103, 105, 107; wireless transmitters111, 113; wireless receivers 115, 117; and compensation components 245,247, which may operate in a similar fashion as described with referenceto FIG. 2, The electronic device 610 also includes the self-interferencenoise calculator 640 and training unit 650 that may provide samplevectors 660 to the self-interference noise calculator 640. Theself-interference noise calculator 500 may be utilized to implement theself-interference noise calculator 640, for example. The training unitmay determine center vectors Ci and the connection weights W_(ij), forexample, by optimizing the minimized error of adjusted signals (e.g,,adjusted signals 508 yi(n) of FIG. 5). For example, an optimizationproblem can be solved utilizing a gradient descent procedure thatcomputes the error, such that the minimized error may be expressed as:

E=Σ _(n=1) ^(M) ∥Y(n)−

∥²   (9)

may be a corresponding desired output vector. To solve this minimizationproblem, the training unit 650 may utilize sample vectors to determinethe center vectors Ci and the connection weights W_(ij).

To determine the center vectors Ci, the training unit 650 may perform acluster analysis (e.g., a k-means cluster algorithm) to determine atleast one center vector among a corresponding set of vectors, such assample vectors 660 based on training points or random vectors. in thesample vector approach, a training point may be selected towards thecenter for each of the sample vectors 660. The training point may becenter of each cluster partition of a set of the sample vectors 660,such that optimizing the cluster center is expressed as minimized erroraway from the cluster center for a given training point in the clusterpartition. Such a relationship may be expressed as:

E _(k_means)=Σ_(j=1) ^(H)Σ_(n=1) ^(M) B _(jn) ∥X(n)−C _(j)∥²   (10)

where B_(jn) is the cluster partition or membership function forming anH×M matrix. Each column of H×M matrix represents an available samplevector and each row of H×M matrix represents a cluster. Each column mayinclude a single “1” in the row corresponding to the cluster nearest tothat training point and zeroes in the other entries of that column. Thetraining unit 650 may initialize the center of each cluster to adifferent randomly chosen training point. Then each training example isassigned by the training unit 650 to a processing element (e.g., aprocessing element 506) nearest to it. When all training points havebeen assigned by the training unit 650, the training unit 650 finds theaverage position of the training point for each cluster and moves thecluster center to that point, when the error away from the clustercenter for each training point is minimized, denoting the set of centervectors Ci for the processing elements (e.g., the processing elements506).

To determine the connection weights W_(ij) for the connections betweenprocessing elements 506 and processing elements 509, the training unit650 may utilize a linear least-squares optimization according to aminimization of the weights expressed as:

$\begin{matrix}{{\min\limits_{W}{\sum_{n = 1}^{M}{{{Y(n)} -}}^{2}}} = {\min\limits_{W}{{{WF} - \hat{Y}}}^{2}}} & (11)\end{matrix}$

where W={W_(ij)} is the L×H matrix of the connection weights, F is anH×M matrix comprising the outputs hi(n) of the processing elements 506,expressed in Equation 11.

may be a corresponding desired output matrix, with an L×M size.Accordingly, in matrix algebra form, connection weight matrix W may beexpressed as

$\begin{matrix}{W = {{\overset{}{Y}F^{+}} = {\overset{}{Y}{\lim\limits_{\alpha\rightarrow 0}{F^{T}\left( {{FF}^{T} + {\alpha \; I}} \right)}^{- 1}}}}} & (12)\end{matrix}$

where F⁺ is the pseudo-inverse of F.

In some examples, for example in the context of self-interferencecalculator 500 implemented as self-interference noise calculator 640, todetermine the connection weights W_(ij) for the connections betweenprocessing elements 506 and processing elements 509, a training unit 650may utilize a batch-processing embodiment where sample sets are readilyavailable (e.g., available to be retrieved from a memory). The trainingunit 650 may randomly initialize the connection weights in theconnection weight matrix W. The output vector Y(n) may be computed inaccordance with Equation 11. An error term e_(i)(n) may be computed foreach processing element 506, which may be expressed as:

e _(i)(n)=y _(i)(n)−

(n) (i=1,2, . . . , L)   (13)

where

_(i) (n) is a corresponding desired output vector. The connectionweights may be adjusted in the batch-processing embodiment in accordancewith a machine learning expression where a γ is the learning-rateparameter which could be fixed or time-varying. In the example, themachine learning expression may be:

W _(ij)(n+1 )=W _(ij)(n)+γe _(i)(n)f _(j)(∥X(n)−C _(i)∥) (i=1,2, . . . ,L; j=1,2, . . . , M)   (14)

Such a process may iterate until passing a specified error threshold. Inthe example, the total error may be expressed as:

ϵ=∥Y(n)−

∥²

Accordingly, the training unit 650 may iterate recursively the processdescribed herein until the error ϵ passes the specified error threshold,such as passing below the specified error threshold.

In some examples, when the training unit 650 is determining the centervectors Ci that are a non-linear set of vectors fitting a Gaussianfunction, a scaling factor σ may be required before determination of theconnection weights W_(ij) for the connections between processingelements 506 and processing elements 509 of a self-interferencecalculator 500 implemented as self-interference calculator 640. In aGaussian function example, a convex hull of the vectors Ci may berequired such that the training points allow a smooth fit for the outputof the processing elements 506. Accordingly, each center vector Ci maybe related to another center vector Ci of the processing elements 506,such that each center vector Ci activates another center vector Ci whencomputing the connection weights. A scaling factor may be based onheuristic that computes the P-nearest neighbor, such that:

$\sigma_{i} = {\frac{1}{P}{\sum_{j = 1}^{P}{{{C_{j} - C_{i}}}^{2}\mspace{14mu} \left( {{i = 1},2,\ldots \mspace{14mu},H} \right)}}}$

where C_(j) (for i=1,2, . . . , H) are the P-nearest neighbors of C_(i).

FIG. 7 is a schematic illustration of a full duplex compensation method700 in accordance with examples described herein. Example method 700 maybe implemented using, for example, electronic device 102, 110 of FIG. 1,electronic device 110 in FIG. 2, electronic device 610, or any system orcombination of the systems depicted in FIGS. 1-2, 5A-5E, or 6 describedherein. The operations described in blocks 708-728 may also be stored ascomputer-executable instructions in a computer-readable medium.

Example method 700 may begin with block 708 that starts execution of theself-interference compensation method and recites “determine vectors forself-interference noise calculator,” In the example, the center vectorsmay be determined according a cluster analysis. For example, an errormay be minimized such that the distance from the cluster center to agiven training point is minimized. Block 708 may be followed by block712 that recites “generate connection weights for self-interferencenoise calculator.” In the example, the connection weights may bedetermined according to a linear least-squares optimization or a batchprocessing embodiment as described herein. Block 712 may be followed byblock 716 that recites “receive signal for transmission atself-interference noise calculator.” Transmitter output data x1(n),x2(n), x3(n), xN(n) 502 may be received as input to a self-interferencenoise calculator. In the example, transmitter output may be a stream oftransmission data from a corresponding transmitter that is performing RFoperations on corresponding signals to be transmitted.

Block 716 may be followed by block 720 that recites “combine signals inaccordance with vectors and connection weights to generate adjustmentsignals based on self-interference noise.” For example, various ALUs,such as multiplication units, in an integrated circuit may be configuredto operate as the circuitry of FIGS. 5A-E, thereby combining thetransmitter output data x1(n), x2(n), x3(n), xN(n) 502 to generateadjusted signals y1(n), y2(n), y3(n), yL(n) 508 as described herein.Block 720 may be followed by a decision block 724 that recites “adjustsignals received at respective antennas with adjustment signals based onself-interference noise.” In the example, compensation components 245,247 may receive the adjusted signals y1(n), y2(n) 241, 243 andcompensate an incoming received wireless transmission from antennas 105,107. In the example, the compensation components 245, 247 may subtractthe adjusted signals y1(n), y2(n) 241, 243 from the received wirelesstransmission to produce compensated received signals for the respectivewireless receivers 115, 117, thereby achieving full duplex compensationmode. Block 724 may be followed by block 728 that ends the examplemethod 700.

In some examples, the blocks 708 and 712 may be an optional block. Forexample, determination of the center vectors and the connection weightsmay occur during a training mode of an electronic device describedherein, while the remaining steps of method 700 may occur during anoperation mode of the electronic devices described herein.

FIG. 8 is a flowchart of a method 800 in accordance with examplesdescribed herein. Example method 800 may be implemented using, forexample, electronic device 102, 110 of FIG. 1, electronic device 110 inFIG. 2, electronic device 610, or any system or combination of thesystems depicted in FIGS. 1-2, 5A-5E, or 6 described herein. In someexamples, the blocks in example method 800 may be performed by acomputing device such as an electronic device 110 of FIG. 1 and/or inconjunction with a processing unit, such as processing unit 512 of FIG.5C-5E. The operations described in blocks 804-828 may also be stored ascomputer-executable instructions in a computer-readable medium such asthe mode configurable control 505, storing the executable instructions515.

Example method 800 may begin with a block 804 that starts execution ofthe mixing input data with coefficient data routine. The method mayinclude a block 808 recites “retrieving a plurality of coefficients froma memory.” As described herein, a processing unit may retrievecoefficients for mixing with input data; for example, utilizing a memorylook-up unit. For example, the memory may store (e.g., in a database)coefficients representative of self-interference noise among variousantennas of an electronic device. For example, the processing unit mayrequest the coefficients from a memory part of the implementingcomputing device, from a memory part of an external computing device, orfrom a memory implemented in a cloud-computing device. In turn, theplurality of coefficients may be retrieved from the memory as requestedby the processing unit.

Block 808 may be followed by block 816 that recites “obtaining inputdata associated with a transmission to be processed at aself-interference noise calculator.” The input data may correspond totransmitter output data x₁(n), x₂(n) 221, 223 that is received as inputdata at a self-interference noise calculator 240 or any of theself-interference noise calculators described herein. Block 816 may befollowed by block 820 that recites “calculating, at a first layer ofmultiplication/accumulation processing units (MAC units), the input dataand delayed versions of respective outputs of the first layer of MACunits with the plurality of coefficients to generate first processingresults.” As described herein, the processing unit utilizes theplurality of coefficients such that mixing the coefficients with inputdata and delayed versions of respective outputs of the first layer ofMAC units generates output data that reflects the processing of theinput data with coefficients by the circuitry of FIGS. 5C, 5D, or 5E.For example, various ALUs in an integrated circuit may be configured tooperate as the circuitry of FIGS. 5C, 5D, or 5E, thereby mixing theinput data and delayed versions of respective outputs of the first layerof MAC units with the coefficients as described herein. For example,with reference to FIG. 5C, the input data and delayed versions ofrespective outputs of the first layer of MAC units may be calculatedwith the plurality of coefficients to generate first processing results,at a first layer of multiplication/accumulation processing units (MACunits). In some examples, various hardware platforms may implement thecircuitry of FIG. 5C, 5D, or 5E, such as an ASIC, a DSP implemented aspart of a FPGA, or a system-on-chip.

Block 816 may be followed by block 820 that recites “calculating, atadditional layers of MAC units, the first processing results and delayedversions of at least a portion of the first processing results with theadditional plurality of coefficients to generate second processingresults.” As described herein, the processing unit utilizes additionalplurality of coefficients such that mixing the coefficients with certainprocessing results and delayed versions of at least a portion of thosecertain processing results generates output data that reflects theprocessing of the input data with coefficients by the circuitry of FIGS.5C, 5D, or 5E. For example, with reference to FIG. 5C, the processingresults of the first layer (e.g., multiplication processing results) anddelayed versions of at least a portion of those processing results maybe calculated with the additional plurality of coefficients to generatesecond processing results, at a second layer ofmultiplication/accumulation processing units (MAC units). The processingresults of the second layer may be calculated with an additionalplurality of coefficients to generate the output data B(1) 530.

Block 820 may be followed by block 824 that recites “providing, from theself-interference noise calculator, output data as adjustment signals tocompensation components.” As described herein, the output data may beprovided to compensation components 245, 247 to compensate or cancelself-interference noise. Once provided, received signals may also beadjusted based on the adjusted signals, such that both signals beingtransmitted and received are simultaneously being processed, therebyachieving full-duplex transmission. Block 824 may be followed by block828 that ends the example method 800. In some examples, the block 808may be an optional block.

The blocks included in the described example methods 700 and 800 are forillustration purposes. In some embodiments, these blocks may beperformed in a different order. In some other embodiments, variousblocks may be eliminated. In still other embodiments, various blocks maybe divided into additional blocks, supplemented with other blocks, orcombined together into fewer blocks. Other variations of these specificblocks are contemplated, including changes in the order of the blocks,changes in the content of the blocks being split or combined into otherblocks, etc.

FIG. 9 illustrates an example of a wireless communications system 900 inaccordance with aspects of the present disclosure. The wirelesscommunications system 900 includes a base station 910, a mobile device915, a drone 917, a small cell 9:30, and vehicles 940, 945. The basestation 910 and small cell 930 may be connected to a network thatprovides access to the Internet and traditional communication links. Thesystem 900 may facilitate a wide-range of wireless communicationsconnections in a 5G system that may include various frequency bands,including but not limited to: a sub-6 GHz band (e.g., 700 MHzcommunication frequency), mid-range communication bands 2.4 GHz), mmWavebands (e.g,. 24 GHz), and a NR band (e.g,, 3.5 GHz).

Additionally or alternatively, the wireless communications connectionsmay support various modulation schemes, including but not limited to:filter bank multi-carrier (FBMC), the generalized frequency divisionmultiplexing (GFDM), universal filtered multi-carrier (UFMC)transmission, bi-orthogonal frequency division multiplexing (BFDM),sparse code multiple access (SCMA), non-orthogonal multiple access(NOMA), multi-user shared access (MUSA), and faster-than-Nyquist (FTN)signaling with time-frequency packing. Such frequency bands andmodulation techniques may be a part of a standards framework, such asLong Term Evolution (LTE) (e.g., 1.8 GHz band) or other technicalspecification published by an organization like 3GPP or IEEE, which mayinclude various specifications for subcarrier frequency ranges, a numberof subcarriers, uplink/downlink transmission speeds, TDD/FDD, and/orother aspects of wireless communication protocols.

The system 900 may depict aspects of a radio access network (RAN), andsystem 900 may be in communication with or include a core network (notshown). The core network may include one or more serving gateways,mobility management entities, home subscriber servers, and packet datagateways. The core network may facilitate user and control plane linksto mobile devices via the RAN, and it may be an interface to an externalnetwork (e.g., the Internet). Base stations 910, communication devices920, and small cells 930 may be coupled with the core network or withone another, or both, via wired or wireless backhaul links (e.g., S1interface, X2 interface, etc.).

The system 900 may provide communication links connected to devices or“things,” such as sensor devices, e.g., solar cells 937, to provide anInternet of Things (“IoT”) framework. Connected things within the IoTmay operate within frequency bands licensed to and controlled bycellular network service providers, or such devices or things may. Suchfrequency bands and operation may be referred to as narrowband IoT(NB-IoT) because the frequency bands allocated for IoT operation may besmall or narrow relative to the overall system bandwidth. Frequencybands allocated for NB-IoT may have bandwidths of 1, 5, 10, or 20 MHz,for example.

Additionally or alternatively, the IoT may include devices or thingsoperating at different frequencies than traditional cellular technologyto facilitate use of the wireless spectrum. For example, an IoTframework may allow multiple devices in system 900 to operate at a sub-6GHz band or other industrial, scientific, and medical (ISM) radio bandswhere devices may operate on a shared spectrum for unlicensed uses. Thesub-6 GHz band may also be characterized as and may also becharacterized as an NB-IoT band. For example, in operating at lowfrequency ranges, devices providing sensor data for “things,” such assolar cells 937, may utilize less energy, resulting in power-efficiencyand may utilize less complex signaling frameworks, such that devices maytransmit asynchronously on that sub-6 GHz band. The sub-6 GHz band maysupport a wide variety of uses case, including the communication ofsensor data from various sensors devices. Examples of sensor devicesinclude sensors for detecting energy, heat, light, vibration, biologicalsignals (e.g., pulse, EEG, EKG, heart rate, respiratory rate, bloodpressure), distance, speed, acceleration, or combinations thereof.Sensor devices may be deployed on buildings, individuals, and/or inother locations in the environment. The sensor devices may communicatewith one another and with computing systems which may aggregate and/oranalyze the data provided from one or multiple sensor devices in theenvironment.

In such a 5G framework, devices may perform functionalities performed bybase stations in other mobile networks (e.g., UMTS or LTE), such asforming a connection or managing mobility operations between nodeshandoff or reselection). For example, mobile device 915 may receivesensor data from the user utilizing the mobile device 915, such as bloodpressure data, and may transmit that sensor data on a narrowband IoTfrequency band to base station 910. In such an example, some parametersfor the determination by the mobile device 915 may include availabilityof licensed spectrum, availability of unlicensed spectrum, and/ortime-sensitive nature of sensor data. Continuing in the example, mobiledevice 915 may transmit the blood pressure data because a narrowband IoTband is available and can transmit the sensor data quickly, identifyinga time-sensitive component to the blood pressure (e.g., if the bloodpressure measurement is dangerously high or low, such as systolic bloodpressure is three standard deviations from norm).

Additionally or alternatively, mobile device 915 may formdevice-to-device (D2D) connections with other mobile devices or otherelements of the system 900, :For example, the mobile device 915 may formRFID, WiFi, MultiFire, Bluetooth, or Zigbee connections with otherdevices, including communication device 920 or vehicle 945. In someexamples, D2D connections may be made using licensed spectrum bands, andsuch connections may be managed by a cellular network or serviceprovider. Accordingly, while the above example was described in thecontext of narrowband 1oT, it can be appreciated that otherdevice-to-device connections may be utilized by mobile device 915 toprovide information (e.g., sensor data) collected on different frequencybands than a frequency band determined by mobile device 915 fortransmission of that information.

Moreover, some communication devices may facilitate ad-hoc networks, forexample, a network being formed with communication devices 920 attachedto stationary objects and the vehicles 940, 945, without a traditionalconnection to a base station 910 and/or a core network necessarily beingformed. Other stationary objects may be used to support communicationdevices 920, such as, but not limited to, trees, plants, posts,buildings, blimps, dirigibles, balloons, street signs, mailboxes, orcombinations thereof. In such a system 900, communication devices 920and small cell 930 (e.g., a small cell, femtocell, WLAN access point,cellular hotspot, etc.) may be mounted upon or adhered to anotherstructure, such as lampposts and buildings to facilitate the formationof ad-hoc networks and other IoT-based networks. Such networks mayoperate at different frequency bands than existing technologies, such asmobile device 915 communicating with base station 910 on a cellularcommunication band.

The communication devices 920 may form wireless networks, operating ineither a hierarchal or ad-hoc network fashion, depending, in part, onthe connection to another element of the system 900. For example, thecommunication devices 920 may utilize a 700 MHz communication frequencyto form a connection with the mobile device 915 in an unlicensedspectrum, while utilizing a licensed spectrum communication frequency toform another connection with the vehicle 945. Communication devices 920may communicate with vehicle 945 on a licensed spectrum to providedirect access for time-sensitive data, for example, data for anautonomous driving capability of the vehicle 945 on a 5.9 GHz band ofDedicated Short Range Communications (DSRC).

Vehicles 940 and 945 may form an ad-hoc network at a different frequencyband than the connection between the communication device 920 and thevehicle 945. For example, for a high bandwidth connection to providetime-sensitive data between vehicles 940, 945, a 24 GHz mmWave band maybe utilized for transmissions of data between vehicles 940, 945. Forexample, vehicles 940, 945 may share real-time directional andnavigation data with each other over the connection while the vehicles940, 945 pass each other across a narrow intersection line. Each vehicle940, 945 may be tracking the intersection line and providing image datato an image processing algorithm to facilitate autonomous navigation ofeach vehicle while each travels along the intersection line. In someexamples, this real-time data may also be substantially simultaneouslyshared over an exclusive, licensed spectrum connection between thecommunication device 920 and the vehicle 945, for example, forprocessing of image data received at both vehicle 945 and vehicle 940,as transmitted by the vehicle 940 to vehicle 945 over the 24 GHz mmWaveband. While shown as automobiles in FIG. 9, other vehicles may be usedincluding, but not limited to, aircraft, spacecraft, balloons, blimps,dirigibles, trains, submarines, boats, ferries, cruise ships,helicopters, motorcycles, bicycles, drones, or combinations thereof.

While described in the context of a 24 GHz mmWave band, it can beappreciated that connections may be formed in the system 900 in othermmWave bands or other frequency bands, such as 28 GHz, 37 GHz, 38 GHz,39 GHz, which may be licensed or unlicensed bands. In some cases,vehicles 940, 945 may share the frequency band that they arecommunicating on with other vehicles in a different network. Forexample, a fleet of vehicles may pass vehicle 940 and, temporarily,share the 24 GHz mmWave band to form connections among that fleet, inaddition to the 24 GHz mmWave connection between vehicles 940, 945. Asanother example, communication device 920 may substantiallysimultaneously maintain a 700 MHz connection with the mobile device 915operated by a user (e.g., a pedestrian walking along the street) toprovide information regarding a location of the user to the vehicle 945over the 5.9 GHz band, In providing such information, communicationdevice 920 may leverage antenna diversity schemes as part of a massiveMIMO framework to facilitate time-sensitive, separate connections withboth the mobile device 915 and the vehicle 945. A massive MIMO frameworkmay involve a transmitting and/or receiving devices with a large numberof antennas _e.g., 12, 20, 64, 128, etc.), which may facilitate precisebeamforming or spatial diversity unattainable with devices operatingwith fewer antennas according to legacy protocols (e.g., WiFi or LTE).

The base station 910 and small cell 930 may wirelessly communicate withdevices in the system 900 or other communication-capable devices in thesystem 900 having at the least a sensor wireless network, such as solarcells 937 that may operate on an active/sleep cycle, and/or one or moreother sensor devices. The base station 910 may provide wirelesscommunications coverage for devices that enter its coverages area, suchas the mobile device 915 and the drone 917. The small cell 930 mayprovide wireless communications coverage for devices that enter itscoverage area, such as near the building that the small cell 930 ismounted upon, such as vehicle 945 and drone 917.

Generally, a small cell 930 may be referred to as a small cell andprovide coverage for a local geographic region, for example, coverage of200 meters or less in some examples. This may contrasted with atmacrocell, which may provide coverage over a wide or large area on theorder of several square miles or kilometers. In some examples, a smallcell 930 may be deployed (e.g., mounted on a building) within somecoverage areas of a base station 910 (e.g., a macrocell) where wirelesscommunications traffic may be dense according to a traffic analysis ofthat coverage area. For example, a small cell 930 may be deployed on thebuilding in FIG. 9 in the coverage area of the base station 910 if thebase station 910 generally receives and/or transmits a higher amount ofwireless communication transmissions than other coverage areas of thatbase station 910. A base station 910 may be deployed in a geographicarea to provide wireless coverage for portions of that geographic area.As wireless communications traffic becomes more dense, additional basestations 910 may be deployed in certain areas, which may alter thecoverage area of an existing base station 910, or other support stationsmay be deployed, such as a small cell 9:30. Small cell 930 may be afemtocell, which may provide coverage for an area smaller than a smallcell (e.g., 100 meters or less in some examples (e.g., one story of abuilding)).

While base station 910 and small cell 930 may provide communicationcoverage for a portion of the geographical area surrounding theirrespective areas, both may change aspects of their coverage tofacilitate faster wireless connections for certain devices. For example,the small cell 930 may primarily provide coverage for devicessurrounding or in the building upon which the small cell 930 is mounted,However, the small cell 930 may also detect that a device has entered iscoverage area and adjust its coverage area to facilitate a fasterconnection to that device.

For example, a small cell 930 may support a massive MIMO connection withthe drone 917, which may also be referred to as an unmanned aerialvehicle (UAV), and, when the vehicle 945 enters it coverage area, thesmall cell 930 adjusts some antennas to point directionally in adirection of the vehicle 945, rather than the drone 917, to facilitate amassive MIMO connection with the vehicle, in addition to the drone 917.In adjusting some of the antennas, the small cell 930 may not support asfast as a connection to the drone 917 at a certain frequency, as it hadbefore the adjustment. For example, the small cell 930 may becommunicating with the drone 917 on a first frequency of variouspossible frequencies in a 4G LTE band of 1.8 GHz. However, the drone 917may also request a connection at a different frequency with anotherdevice (e.g., base station 910) in its coverage area that may facilitatea similar connection as described with reference to the small cell 930,or a different (e.g., faster, more reliable) connection with the basestation 910, for example, at a 3.5 GHz frequency in the 5G NR band.Accordingly, the system 900 may enhance existing communication links inproviding additional connections to devices that may utilize or demandsuch links, while also compensating for any self-interference noisegenerated by the drone 917 in transmitting, for example, in both the 4GELIE and 5G NR bands. In some examples, drone 917 may serve as a movableor aerial base station.

The wireless communications system 900 may include devices such as basestation 910, communication device 920, and small cell 930 that maysupport several connections at varying frequencies to devices in thesystem 900, while also compensating for self-interference noiseutilizing self-interference noise calculators, such as self-interferencenoise calculator 240 or 500. Such devices may operate in a hierarchalmode or an ad-hoc mode with other devices in the network of system 900,While described in the context of a base station 910, communicationdevice 920, and small cell 930, it can be appreciated that other devicesthat can support several connections with devices in the network, whilealso compensating for self-interference noise utilizingself-interference noise calculators, may be included in system 900,including but not limited to: macrocells, femtocells, routers,satellites, and RFID detectors.

In various examples, the elements of wireless communication system 900,such as base station 910, a mobile device 915, a drone 917,communication device 920 a small cell 930, and vehicles 940, 945, may beimplemented as an electronic device described herein that compensate forself-interference noise utilizing self-interference noise calculators.For example, the communication device 920 may be implemented aselectronic devices described herein, such as electronic device 102, 110of FIG. 1, electronic device 110 in FIG. 2, electronic device 610, orany system or combination of the systems depicted in FIGS. 1-2, 5A-5E,or 6 described herein, or any system or combination of the systemsdepicted in the Figures described herein.

FIG. 10 illustrates an example of a wireless communications system 1000in accordance with aspects of the present disclosure. The wirelesscommunications system 1000 includes a mobile device 1015, a drone 1017,a communication device 1020, and a small cell 1030. A building 1010 alsoincludes devices of the wireless communication system 1000 that may beconfigured to communicate with other elements in the building 1010 orthe small cell 1030. The building 1010 includes networked workstations1040, 1045, virtual reality device 1050, IoT devices 1055, 1060, andnetworked entertainment device 1065. in the depicted system 1000, IoTdevices 1055, 1060 may be a washer and dryer, respectively, forresidential use, being controlled by the virtual reality device 1050.Accordingly, while the user of the virtual reality device 1050 may be indifferent room of the building 1010, the user may control an operationof the IoT device 1055, such as configuring a washing machine setting.Virtual reality device 1050 may also control the networked entertainmentdevice 1065. For example, virtual reality device 1050 may broadcast avirtual game being played by a user of the virtual reality device 1050onto a display of the networked entertainment device 1065.

The small cell 1030 or any of the devices of building 1010 may beconnected to a network that provides access to the Internet andtraditional communication links. Like the system 900, the system 1000may facilitate a wide-range of wireless communications connections in a5G system that may include various frequency bands, including but notlimited to: a sub-6 GHz band (e.g., 700 MHz communication frequency),mid-range communication bands (e.g., 2.4 GHz), and mmWave bands (e.g,.24 GHz). Additionally or alternatively, the wireless communicationsconnections may support various modulation schemes as described abovewith reference to system 900. System 1000 may operate and be configuredto communicate analogously to system 900. Accordingly, similarlynumbered elements of system 1000 and system 900 may be configured in ananalogous way, such as communication device 920 to communication device1020, small cell 930 to small cell 1030, etc.

Like the system 900, where elements of system 900 are configured to formindependent hierarchal or ad-hoc networks, communication device 1020 mayform a hierarchal network with small cell 1030 and mobile device 1015,while an additional ad-hoc network may be formed among the small cell1030 network that includes drone 1017 and some of the devices of thebuilding 1010, such as networked workstations 1040, 1045 and IoT devices1055, 1060,

Devices in communication system 1000 may also form (D2D) connectionswith other mobile devices or other elements of the system 1000. Forexample, the virtual reality device 1050 may form a narrowband IoTconnections with other devices, including IoT device 1055 and networkedentertainment device 1065. As described above, in some examples, D2Dconnections may be made using licensed spectrum hands, and suchconnections may be managed by a cellular network or service provider.Accordingly, while the above example was described in the context of anarrowband JoT, it can be appreciated that other device-to-deviceconnections may be utilized by virtual reality device 1050.

In various examples, the elements of wireless communication system 1000,such as the mobile device 1015, the drone 1017, the communication device1020, and the small cell 1030, the networked workstations 1040, 1045,the virtual reality device 1050, the IoT devices 1055, 1060, and thenetworked entertainment device 1065, may be implemented as electronicdevices described herein that compensate for self-interference noiseutilizing self-interference noise calculators. For example, thecommunication device 1020 may be implemented as electronic devicesdescribed herein, such as electronic device 102, 110 of FIG. 1,electronic device 110 in FIG. 2, electronic device 610, or any system orcombination of the systems depicted in FIGS. 1-2, 5A-5E, or 6 describedherein, or any system or combination of the systems depicted in theFigures described herein.

Certain details are set forth above to provide a sufficientunderstanding of described examples. However, it will be clear to oneskilled in the art that examples may be practiced without various ofthese particular details. The description herein, in connection with theappended drawings, describes example configurations and does notrepresent all the examples that may be implemented or that are withinthe scope of the claims. The terms “exemplary” and “example” as may beused herein means “serving as an example, instance, or illustration,”and not “preferred” or “advantageous over other examples.” The detaileddescription includes specific details for the purpose of providing anunderstanding of the described techniques. These techniques, however,may be practiced without these specific details. In some instances,well-known structures and devices are shown in block diagram form inorder to avoid obscuring the concepts of the described examples.

Information and signals described herein may be represented using any ofa variety of different technologies and techniques. For example, data,instructions, commands, information, signals, bits, symbols, and chipsthat may be referenced throughout the above description may berepresented by voltages, currents, electromagnetic waves, magneticfields or particles, optical fields or particles, or any combinationthereof.

Techniques described herein may be used for various wirelesscommunications systems, which may include multiple access cellularcommunication systems, and which may employ code division multipleaccess (CDMA), time division multiple access (TDMA), frequency divisionmultiple access (FDMA), orthogonal frequency division multiple access(OFDMA), or single carrier frequency division multiple access (SC-FDMA),or any a combination of such techniques. Some of these techniques havebeen adopted in or relate to standardized wireless communicationprotocols by organizations such as Third Generation Partnership Project(3GPP), Third Generation Partnership Project 2 (3GPP2) and IEEE. Thesewireless standards include Ultra Mobile Broadband (UMB), UniversalMobile Telecommunications System (UMTS), Long Term Evolution (LTE),LTE-Advanced (LTE-A), LTE-A Pro, New Radio (NR), IEEE 802.11 (WiFi), andIEEE 802.16 (WiMAX), among others.

The terms “5G” or “5G communications system” may refer to systems thatoperate according to standardized protocols developed or discussedafter, for example, LTE Releases 13 or 14 or WiMAX 802.16e-2005 by theirrespective sponsoring organizations. The features described herein maybe employed in systems configured according to other generations ofwireless communication systems, including those configured according tothe standards described above.

The various illustrative blocks and modules described in connection withthe disclosure herein may be implemented or performed with ageneral-purpose processor, a digital signal processor (DSP), anapplication-specific integrated circuit (ASIC), a field-programmablegate array (FPGA), or other programmable logic device, discrete gate ortransistor logic, discrete hardware components, or any combinationthereof designed to perform the functions described herein. Ageneral-purpose processor may be a microprocessor, but in thealternative, the processor may be any conventional processor,controller, microcontroller, or state machine. A processor may also beimplemented as a combination of computing devices (e.g., a combinationof a DSP and a microprocessor, multiple microprocessors, one or moremicroprocessors in conjunction with a DSP core, or any other suchconfiguration).

The functions described herein may be implemented in hardware, softwareexecuted by a processor, firmware, or any combination thereof. Ifimplemented in software executed by a processor, the functions may bestored on or transmitted over as one or more instructions or code on acomputer-readable medium. Computer-readable media includes bothnon-transitory computer storage media and communication media includingany medium that facilitates transfer of a computer program from oneplace to another. A non-transitory storage medium may be any availablemedium that can be accessed by a general purpose or special purposecomputer. By way of example, and not limitation, non-transitorycomputer-readable media can comprise RAM, ROM, electrically erasableprogrammable read only memory (EEPROM), or optical disk storage,magnetic disk storage or other magnetic storage devices, or any othernon-transitory medium that can be used to carry or store desired programcode means in the form of instructions or data structures and that canbe accessed by a general-purpose or special-purpose computer, or ageneral-purpose or special-purpose processor.

Also, any connection is properly termed a computer-readable medium. Forexample, if the software is transmitted from a website, server, or otherremote source using a coaxial cable, fiber optic cable, twisted pair,digital subscriber line (DSL), or wireless technologies such asinfrared, radio, and microwave, then the coaxial cable, fiber opticcable, twisted pair, DSL, or wireless technologies such as infrared,radio, and microwave are included in the definition of medium.Combinations of the above are also included within the scope ofcomputer-readable media.

Other examples and implementations are within the scope of thedisclosure and appended claims. For example, due to the nature ofsoftware, functions described above can be implemented using softwareexecuted by a processor, hardware, firmware, hardwiring, or combinationsof any of these. Features implementing functions may also be physicallylocated at various positions, including being distributed such thatportions of functions are implemented at different physical locations.

Also, as used herein, including in the claims, “or” as used in a list ofitems (for example, a list of items prefaced by a phrase such as “atleast one of” or “one or more of”) indicates an inclusive list suchthat, for example, a list of at least one of A, B, or C means A or B orC or AB or AC or BC or ABC (i.e., A and B and C). Also, as used herein,the phrase “based on” shall not be construed as a reference to a closedset of conditions. For example, an exemplary step that is described as“based on condition A” may be based on both a condition A and acondition B without departing from the scope of the present disclosure.In other words, as used herein, the phrase “based on” shall be construedin the same manner as the phrase “based at least in part on.”

From the foregoing it will be appreciated that, although specificexamples have been described herein for purposes of illustration,various modifications may be made while remaining with the scope of theclaimed technology. The description herein is provided to enable aperson skilled in the art to make or use the disclosure. Variousmodifications to the disclosure will be readily apparent to thoseskilled in the art, and the generic principles defined herein may beapplied to other variations without departing from the scope of thedisclosure. Thus, the disclosure is not limited to the examples anddesigns described herein, but is to be accorded the broadest scopeconsistent with the principles and novel features disclosed herein.

1. An apparatus comprising: a plurality of transmitting antennas;plurality of receiving antennas; a plurality of wireless transmittersconfigured to transmit a respective plurality of transmit signals from arespective transmitting antenna of the plurality of transmittingantennas; a plurality of wireless receivers configured to receive arespective plurality of receive signals from a respective receivingantenna of the plurality of receiving antennas; a self-interferencenoise calculator coupled to the plurality of transmitting antennas andthe plurality of receiving antennas, the self-interference noisecalculator configured to generate a plurality of adjusted signals, theself-interference noise calculator comprising: a first layer ofmultiplication/accumulation units (MAC units) of a plurality of layersof MAC units configured to mix the plurality of transmit signals asinput data and delayed versions of respective outputs of the first layerof MAC units using a plurality of coefficients to generate firstintermediate processing results; and additional layers of MAC units ofthe plurality of layers of MAC units, each additional layer of MAC unitsconfigured to mix the first intermediate processing results and delayedversions of respective outputs of the respective additional layer of MACunits using additional coefficients of the plurality of coefficients togenerate second intermediate processing results, wherein theself-interference noise calculator is configured to provide theplurality of adjusted signals as output data, the output data basedpartly on the second intermediate processing results; and wherein eachwireless receiver is configured to receive a corresponding adjustedsignal of the plurality of adjusted signals.
 2. The apparatus of claim1, wherein the self-interference noise calculator is configured togenerate the plurality of adjusted signals based on calculations ofself-interference noise for the plurality of transmit signals.
 3. Theapparatus of claim 2, further comprising; a plurality of compensationcomponents, each compensation component coupled to an input of, thewireless receiver and configured to generate a respective compensatedreceived signal based on the plurality of adjusted signals.
 4. Theapparatus of claim 3, wherein the self-interference noise calculator isconfigured to transmit a respective adjustment signals to a respectivecompensation component.
 5. The apparatus of claim 3, wherein eachcompensation component coupled to a respective output of a respectivereceiving antenna of the plurality of receiving antennas and configuredto receive a respective radio frequency (RF) signal.
 6. The apparatus ofclaim 5, wherein each compensation component configured to subtract arespective adjusted signal from the respective RF signal to generate therespective compensated received signal.
 7. The apparatus of claim 1,wherein as number of the plurality of layers of MAC units corresponds toa number of transmitting antennas of the plurality of transmittingantennas.
 8. The apparatus of claim 1, further comprising: a pluralityof memory look up units (MLUs) configured to store and providerespective the first or second intermediate processing results, whereina portion of the plurality of memory look up units configured to provideoutput data according to the input data being mixed using the pluralityof coefficients.
 9. The apparatus of claim 8 further comprising: aplurality of delay units configured to provide the delayed versions ofthe respective outputs of the first layer a MAC units based on the firstor second intermediate processing results provided by respective MLUs ofthe plurality of MLUs.
 10. The apparatus of claim 1, wherein eachcoefficient of the plurality of coefficients is representative of avector of self-interference of a respective wireless path to a firsttransmitting antenna of the plurality of antennas from at least oneother transmitting antenna of the plurality of transmitting antennas.11. The apparatus of claim 1, wherein the plurality of coefficients arebased on training of a recurrent neural network.
 12. An apparatuscomprising: a plurality of antennas, each antenna configured to transmita respective wireless communications signal; a self-interference noisecalculator coupled to each antenna of the plurality of antennas, theself-interference noise calculator comprising: a plurality of bitmanipulation units, each hit manipulation unit configured to receive therespective wireless communications signal; and a plurality ofmultiplication/accumulation (MAC) units, each MAC unit configured togenerate a plurality of noise processing results based on the respectivewireless communications signal and a delayed version of at least one ofthe plurality of noise processing results.
 13. The apparatus of claim12, further comprising: a plurality of memory look-up units (MLUs)configured to store and provide respective noise processing results,wherein a portion of the plurality of the MLUs configured to provideoutput data based on the is data being mixed using a plurality ofcoefficients.
 14. The apparatus of claim 13, further comprising: aplurality of delay units, each delay unit associated with a respectiveMAC unit and configured to provide the delayed versions of respectiveoutputs of the plurality of MAC units based on a portion of therespective noise processing results provided b respective MLUs of theplurality of MLUs.
 15. The apparatus of claim 13, further comprising: amemory database configured to provide the plurality of coefficients tothe plurality of MLUs.
 16. The apparatus of claim 13, wherein eachcoefficient of the plurality of coefficients is representative of avector of self-interference of a respective wireless path to a firstantenna of the plurality of antennas from at least one other antenna ofthe plurality of antennas.
 17. A method comprising: receiving aplurality of signals associated with a transmission at aself-interference noise calculator; mixing, at the self-interferencecalculator, the plurality of signals as input data using a plurality ofcoefficients and additional plurality of coefficients, wherein mixingthe input data comprises: calculating, at a first layer ofmultiplication/accumulation processing units (MAC units) of a pluralityof MAC units, the input data and delayed versions of respective outputsof the first layer of MAC units with the plurality of coefficients togenerate first processing results; and calculating, at additional layersof MAC units of the plurality of MAC units, the first processing resultsand delayed versions of respective outputs of a respective additionallayer of MAC units with the additional plurality of coefficients togenerate second processing results; providing, from theself-interference noise calculator, output data as a plurality ofadjustment signals, the output data based partly on the secondprocessing results,
 18. The method of claim 17, further comprising:adjusting a plurality of signals received at respective antennas of theplurality of antennas with a corresponding adjustment signal of theplurality of adjustment signals.
 19. The method of claim 17, furthercomprising: transmitting the plurality of signals to be transmitted at afirst frequency band of a plurality of frequency bands; andsimultaneously receiving the plurality of signals received at respectiveantennas of a plurality of antennas.
 20. The method of claim 19, whereina number of the additional layers of MAC units is associated with anumber of the plurality of antennas.